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DeviceOperating
Temperature Range Package
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ORDERING INFORMATION
MC33215FB
MC33215BTA = –20° to +70°C
TQFP–52
SDIP–42
B SUFFIXPLASTIC PACKAGE
CASE 858(SDIP–42)
Order this document by MC33215/D
FB SUFFIXPLASTIC PACKAGE
CASE 848B(TQFP–52)
52 1
42
1
1MOTOROLA ANALOG IC DEVICE DATA
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The MC33215 is developed for use in fully electronic telephone sets withspeakerphone functions. The circuit performs the ac and dc line termination,2–4 wire conversion, line length AGC and DTMF transmission. Thespeakerphone part includes a half duplex controller with signal and noisemonitoring, base microphone and loudspeaker amplifiers and an efficientsupply. The circuit is designed to operate at low line currents down to 4.0 mAenabling parallel operation with a classical telephone set.
• Highly Integrated Cost Effective Solution• Straightforward AC and DC Parameter Adjustments• Efficient Supply for Loudspeaker Amplifier and Peripherals• Stabilized Supply Point for Handset Microphone• Stabilized Supply Point for Base Microphone• Loudspeaker Amplifier can be Powered and Used Separately• Smooth Switch–Over from Handset to Speakerphone Operation• Adjustable Switching Depth for Handsfree Operation
Simplified Application
This device contains 2782 active transistors.
Attenuator
DTMF
Attenuator
DuplexController
LineDriver
CurrentSplitter
1:10
HandsetMicrophone
BaseMicrophone
VCC or External Supply
Base Loudspeaker
Auxiliary Input
Handset Earpiece
Receive Signal
TelephoneLine
VCC Supply
DC Slope
Line CurrentDC Offset
ACImpedance
RxLS
BM
HM
MF
This document contains information on a new product. Specifications and information hereinare subject to change without notice.
Motorola, Inc. 1997 Rev 0
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MC33215
2 MOTOROLA ANALOG IC DEVICE DATA
FEATURES
Line Driver and Supply• AC and DC Termination of Telephone Line• Adjustable Set Impedance for Real and Complex
Termination• Efficient Supply Point for Loudspeaker Amplifier and
Peripherals• Two Stabilized Supply Points for Handset and Base
Microphones• Separate Supply Arrangement for Handset and
Speakerphone Operation
Handset Operation• Transmit and Receive Amplifiers• Differential Microphone Inputs• Sidetone Cancellation Network• Line Length AGC• Microphone and Earpiece Mute
• Separate Input for DTMF and Auxiliary Signals• Parallel Operation Down to 4.0 mA of Line Current
Speakerphone Operation• Handsfree Operation via Loudspeaker and Base
Microphone• Integrated Microphone and Loudspeaker Amplifiers• Differential Microphone Inputs• Loudspeaker Amplifier can be Powered and Used
Separately from the Rest of the Circuit• Integrated Switches for Smooth Switch–Over from
Handset to Speakerphone Operation• Signal and Background Noise Monitoring in Both
Channels• Adjustable Switching Depth for Handsfree Operation• �������� Switch–Over ��� �� ��� �����
• Dial Tone Detector in the Receive Channel
TQFP–52
Figure 1. Pin Connections
1
2
3
4
5
6
7
8
9
10
11
12
13
14
15
16
17
18
19
20
21
42
41
40
39
38
37
36
35
34
33
32
31
30
29
28
27
26
25
24
23
22
1
2
3
4
5
6
7
8
9
10
11
12
13
14 15 16 17 18 19 20 21 22 23 24 25 26
39
38
37
36
35
34
33
32
31
30
29
28
27
52 51 50 49 48 47 46 45 44 43 42 41 40
SLB
REG
SLP
MFI
HM1
HM2
BM2
BM1
VDD
TSA
TSE
TBN
MUT
LSF
BVO
PPL
LSI
VOL
SWD
REF
AGC
Gnd
RLS
RSA
RSE
RBN
SLB
REG
SLP
MFI
HM1
HM2
BM2
BM1
VDD
TSA
TSE
TBN
MUT
VCC
VLN
VHF
VMC
SPS
PRS
SWT
LSM
LSF
BVO
PPL
LSI
VOL
SWD
REF
AGC
Gnd
RLS
RSA
RSE
RBN
RXI
GRX
RXO
RXS
PGD
LSO
VLS
LSB
(Top View)
(Top View)
N/C
N/C
N/C
N/C
SPS
PRS
SWT
LSM
N/C
RXS
RXO
GR
X
RXI
N/C
N/C
N/C
N/C
VMC
VHF
VLN
CC
N/C
PGD
LSO
VLS
LSB
V
SDIP–42
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MC33215
3MOTOROLA ANALOG IC DEVICE DATA
MAXIMUM RATINGS
Rating Min Max Unit
Peak Voltage at VLN –0.5 12 V
Maximum Loop Current – 160 mA
Voltage at VLS (if Powered Separately) –0.5 12 V
Voltage at VHF (if Externally Applied) –0.5 5.5 V
Voltage at SPS, MUT, PRS, LSM –0.5 7.5 V
Maximum Junction Temperature – 150 °C
Storage Temperature Range –65 150 °C
NOTE: ESD data available upon request.
RECOMMENDED OPERATING CONDITIONS
Characteristic Min Max Unit
Biasing Voltage at VLN 2.4 10 V
Loop Current 4.0 130 mA
Voltage at VLS 2.4 8.0 V
Voltage at VHF (if Externally Applied) 2.4 5.0 V
Voltage at SPS, MUT, PRS, LSM 0 5.0 V
Operating Ambient Temperature Range –20 70 °C
ELECTRICAL CHARACTERISTICS (All parameters are specified at T = 25°C, Iline = 18 mA, VLS = 2.9 V, f = 1000 Hz,PRS = high, MUT = high, SPS = low, LSM = high, test figure in Figure 17 with S1 in position 1, unless otherwise stated.)
Characteristic Min Typ Max UnitÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁ
DC LINE VOLTAGEÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁ
Line Voltage Vline ÁÁÁÁÁÁÁÁÁÁ
ÁÁÁÁÁÁÁÁ
ÁÁÁÁÁÁÁÁ
ÁÁÁÁÁÁÁÁ
VParallel Operation, Iline = 4.0 mA – 2.4 –
ÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁIline = 20 mA ÁÁÁÁÁ3.9 ÁÁÁÁ4.2 ÁÁÁÁ4.5 ÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁ
Iline = 70 mAÁÁÁÁÁÁÁÁÁÁ
4.8 ÁÁÁÁÁÁÁÁ
5.2 ÁÁÁÁÁÁÁÁ
5.6 ÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁ
ÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁSUPPLY POINT VDD
ÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁ
Internal Current Consumption from VDD ÁÁÁÁÁÁÁÁÁÁ
– ÁÁÁÁÁÁÁÁ
1.2 ÁÁÁÁÁÁÁÁ
1.5 ÁÁÁÁÁÁÁÁ
mAVDD = 2.5 VÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁ
ÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁSUPPLY POINT VMCÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁDC Voltage at VMC (= VMC0)
ÁÁÁÁÁÁÁÁÁÁ1.6
ÁÁÁÁÁÁÁÁ1.75
ÁÁÁÁÁÁÁÁ1.9
ÁÁÁÁÁÁÁÁVÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁ
ÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁCurrent Available from VMCÁÁÁÁÁÁÁÁÁÁ1.0
ÁÁÁÁÁÁÁÁ–
ÁÁÁÁÁÁÁÁ–
ÁÁÁÁÁÁÁÁmAVMC = VMC0 – 200 mV
ÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁ
SUPPLY POINT VHF
ÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁ
DC Voltage at VHF (= VHF0) ÁÁÁÁÁÁÁÁÁÁ
2.6 ÁÁÁÁÁÁÁÁ
2.8 ÁÁÁÁÁÁÁÁ
3.0 ÁÁÁÁÁÁÁÁ
V
ÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁ
Internal Current Consumption from VHF ÁÁÁÁÁÁÁÁÁÁ
– ÁÁÁÁÁÁÁÁ
1.4 ÁÁÁÁÁÁÁÁ
2.0 ÁÁÁÁÁÁÁÁ
mAVHF = VHF0 + 100 mVÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁ
ÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁCurrent Available from VHFÁÁÁÁÁÁÁÁÁÁ2.0
ÁÁÁÁÁÁÁÁ–
ÁÁÁÁÁÁÁÁ–
ÁÁÁÁÁÁÁÁmAVHF = VHF0 – 300 mV
ÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁ
SUPPLY POINT VCCÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁ
Current Available from VCC ÁÁÁÁÁÁÁÁÁÁ
13 ÁÁÁÁÁÁÁÁ
15 ÁÁÁÁÁÁÁÁ
– ÁÁÁÁÁÁÁÁ
mA
ÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁ
VCC = 2.4 V, Iline = 20 mA ÁÁÁÁÁÁÁÁÁÁ
ÁÁÁÁÁÁÁÁ
ÁÁÁÁÁÁÁÁ
ÁÁÁÁÁÁÁÁ
ÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁDC Voltage Drop Between VLN and VCC
ÁÁÁÁÁÁÁÁÁÁ–
ÁÁÁÁÁÁÁÁ1.0
ÁÁÁÁÁÁÁÁ1.5
ÁÁÁÁÁÁÁÁVÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁ
ÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁIline = 20 mA
ÁÁÁÁÁÁÁÁÁÁ
ÁÁÁÁÁÁÁÁ
ÁÁÁÁÁÁÁÁ
ÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁ
ÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁSUPPLY INPUT VLS
ÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁ
Internal Current Consumption from VLS ÁÁÁÁÁÁÁÁÁÁ
– ÁÁÁÁÁÁÁÁ
1.0 ÁÁÁÁÁÁÁÁ
1.5 ÁÁÁÁÁÁÁÁ
mA
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MC33215
4 MOTOROLA ANALOG IC DEVICE DATA
ELECTRICAL CHARACTERISTICS (continued) (All parameters are specified at T = 25°C, Iline = 18 mA, VLS = 2.9 V, f = 1000 Hz,PRS = high, MUT = high, SPS = low, LSM = high, test figure in Figure 17 with S1 in position 1, unless otherwise stated.)
Characteristic UnitMaxTypMin
ÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁ
LOGIC INPUTS
Logic Low Level Pins PRS, MUT, SPS, LSM – – 0.4 V
Logic High Level Pins PRS, MUT, SPS, LSM 2.0 – 5.0 V
Internal Pull Up Pins PRS, MUT, LSM – 100 – kΩ
ÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁ
Internal Pull Down Pin SPS ÁÁÁÁÁÁÁÁÁÁ
– ÁÁÁÁÁÁÁÁ
100 ÁÁÁÁÁÁÁÁ
– ÁÁÁÁÁÁÁÁ
kΩ
ÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁ
Tx CHANNEL, HANDSET MICROPHONE AMPLIFIER
ÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁ
Voltage Gain from VHM to Vline ÁÁÁÁÁÁÁÁÁÁ
46 ÁÁÁÁÁÁÁÁ
47 ÁÁÁÁÁÁÁÁ
48 ÁÁÁÁÁÁÁÁ
dBVHM = 1.5 mVrmsÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁ
ÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁGain Reduction in Mute Condition
ÁÁÁÁÁÁÁÁÁÁ
60ÁÁÁÁÁÁÁÁ
–ÁÁÁÁÁÁÁÁ
–ÁÁÁÁÁÁÁÁ
dBMUT = Low or PRS = Low or SPS = High
ÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁ
Input Impedance at HM1 and HM2 ÁÁÁÁÁÁÁÁÁÁ
14 ÁÁÁÁÁÁÁÁ
18 ÁÁÁÁÁÁÁÁ
22 ÁÁÁÁÁÁÁÁ
kΩ
ÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁ
Common Mode Rejection Ratio ÁÁÁÁÁÁÁÁÁÁ
– ÁÁÁÁÁÁÁÁ
50 ÁÁÁÁÁÁÁÁ
– ÁÁÁÁÁÁÁÁ
dB
ÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁ
Total Harmonic Distortion at VLN ÁÁÁÁÁÁÁÁÁÁ
– ÁÁÁÁÁÁÁÁ
– ÁÁÁÁÁÁÁÁ
2.0 ÁÁÁÁÁÁÁÁ
%VHM = 4.5 mVrmsÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁ
ÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁPsophometrically Weighted Noise Level at VlineÁÁÁÁÁÁÁÁÁÁ–
ÁÁÁÁÁÁÁÁ–72
ÁÁÁÁÁÁÁÁ–
ÁÁÁÁÁÁÁÁdBmpHM1 and HM2 Shorted with 200 Ω
ÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁ
Tx CHANNEL, BASE MICROPHONE AMPLIFIER (SPS = HIGH, T x MODE FORCED)
ÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁ
Voltage Gain from VBM to Vline ÁÁÁÁÁÁÁÁÁÁ
53 ÁÁÁÁÁÁÁÁ
55.5 ÁÁÁÁÁÁÁÁ
58 ÁÁÁÁÁÁÁÁ
dBVBM = 0.5 mVrmsÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁ
ÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁInput Impedance at BM1 and BM2ÁÁÁÁÁÁÁÁÁÁ14
ÁÁÁÁÁÁÁÁ18
ÁÁÁÁÁÁÁÁ22
ÁÁÁÁÁÁÁÁkΩÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁ
ÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁCommon Mode Rejection RatioÁÁÁÁÁÁÁÁÁÁ–
ÁÁÁÁÁÁÁÁ50
ÁÁÁÁÁÁÁÁ–
ÁÁÁÁÁÁÁÁdBÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁ
ÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁTotal Harmonic Distortion at VLNÁÁÁÁÁÁÁÁÁÁ–
ÁÁÁÁÁÁÁÁ–
ÁÁÁÁÁÁÁÁ2.0
ÁÁÁÁÁÁÁÁ%VBM = 1.5 mV
ÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁ
Psophometrically Weighted Noise Level at Vline ÁÁÁÁÁÁÁÁÁÁ
– ÁÁÁÁÁÁÁÁ
–62 ÁÁÁÁÁÁÁÁ
– ÁÁÁÁÁÁÁÁ
dBmpBM1 and BM2 Shorted with 200 Ω
ÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁGain Reduction in Mute Condition ÁÁÁÁÁ60 ÁÁÁÁ– ÁÁÁÁ– ÁÁÁÁdBMUT = Low or PRS = Low or SPS = Low
ÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁ
Tx CHANNEL, DTMF AMPLIFIER (MUT = LOW OR PRS = LOW)ÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁ
Voltage Gain from VMF to VlineÁÁÁÁÁÁÁÁÁÁ
34 ÁÁÁÁÁÁÁÁ
35 ÁÁÁÁÁÁÁÁ
36 ÁÁÁÁÁÁÁÁ
dBVMF = 7.5 mVrms
ÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁ
Input Impedance at MFI ÁÁÁÁÁÁÁÁÁÁ
14 ÁÁÁÁÁÁÁÁ
18 ÁÁÁÁÁÁÁÁ
22 ÁÁÁÁÁÁÁÁ
kΩ
ÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁ
Gain Reduction in Mute Condition ÁÁÁÁÁÁÁÁÁÁ
60 ÁÁÁÁÁÁÁÁ
– ÁÁÁÁÁÁÁÁ
– ÁÁÁÁÁÁÁÁ
dBMUT = High or PRS = Low
ÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁ
Rx CHANNEL, EARPIECE AMPLIFIERÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁ
Voltage Gain from VRXI to VEAR (Note 1)ÁÁÁÁÁÁÁÁÁÁ
23 ÁÁÁÁÁÁÁÁ
24 ÁÁÁÁÁÁÁÁ
25 ÁÁÁÁÁÁÁÁ
dBVline = 20 mVrms
ÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁ
Gain Reduction in Mute Condition ÁÁÁÁÁÁÁÁÁÁ
60 ÁÁÁÁÁÁÁÁ
– ÁÁÁÁÁÁÁÁ
– ÁÁÁÁÁÁÁÁ
dBMUT = Low or SPS = LowÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁ
ÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁInput Impedance at RXI
ÁÁÁÁÁÁÁÁÁÁ
24ÁÁÁÁÁÁÁÁ
30ÁÁÁÁÁÁÁÁ
36ÁÁÁÁÁÁÁÁ
kΩÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁ
Psophometrically Weighted Noise Level at VEARÁÁÁÁÁÁÁÁÁÁ
–ÁÁÁÁÁÁÁÁ
130ÁÁÁÁÁÁÁÁ
–ÁÁÁÁÁÁÁÁ
µVrmsRXI Shorted to Gnd via 10 µF
ÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁ
Confidence Level During DTMF Dialing ÁÁÁÁÁÁÁÁÁÁ
10 ÁÁÁÁÁÁÁÁ
15 ÁÁÁÁÁÁÁÁ
20 ÁÁÁÁÁÁÁÁ
mVrmsVMF = 7.5 mVrms, MUT = LowÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁ
ÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁOutput Swing Capability into 150 ΩÁÁÁÁÁÁÁÁÁÁ680
ÁÁÁÁÁÁÁÁ–
ÁÁÁÁÁÁÁÁ–
ÁÁÁÁÁÁÁÁmVppTHD ≤2%
ÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁ
Output Swing Capability into 450 Ω ÁÁÁÁÁÁÁÁÁÁ
1800 ÁÁÁÁÁÁÁÁ
– ÁÁÁÁÁÁÁÁ
– ÁÁÁÁÁÁÁÁ
mVppTHD ≤2%, RRXO = 360 kΩ
NOTE: 1. Corresponding to –0.6 dB gain from the line to output RXO in the typical application.
Fre
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MC33215
5MOTOROLA ANALOG IC DEVICE DATA
ELECTRICAL CHARACTERISTICS (continued) (All parameters are specified at T = 25°C, Iline = 18 mA, VLS = 2.9 V, f = 1000 Hz,PRS = high, MUT = high, SPS = low, LSM = high, test figure in Figure 17 with S1 in position 1, unless otherwise stated.)
Characteristic UnitMaxTypMin
ÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁ
Rx CHANNEL, LOUDSPEAKER PRE–AMPLIFIER (SPS = HIGH, R x MODE FORCED)
ÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁ
Voltage Gain from VRXI to VRLS (Note 2) ÁÁÁÁÁÁÁÁÁÁ
21 ÁÁÁÁÁÁÁÁ
24 ÁÁÁÁÁÁÁÁ
27 ÁÁÁÁÁÁÁÁ
dBVline = 20 mVrmsÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁ
ÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁGain Reduction in Mute ConditionÁÁÁÁÁÁÁÁÁÁ60
ÁÁÁÁÁÁÁÁ–
ÁÁÁÁÁÁÁÁ–
ÁÁÁÁÁÁÁÁdBSPS = Low or MUT = Low
ÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁ
Rx CHANNEL, LOUDSPEAKER AMPLIFIER
ÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁ
Voltage Gain from VLSI to VLSP ÁÁÁÁÁÁÁÁÁÁ
25 ÁÁÁÁÁÁÁÁ
26 ÁÁÁÁÁÁÁÁ
27 ÁÁÁÁÁÁÁÁ
dBVLSI = 10 mVrmsÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁ
ÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁAttenuation at Delta RVOL = 47 kΩÁÁÁÁÁÁÁÁÁÁ–
ÁÁÁÁÁÁÁÁ32
ÁÁÁÁÁÁÁÁ–
ÁÁÁÁÁÁÁÁdBÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁ
ÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁPsophometrically Weighted Noise Level at VLSPÁÁÁÁÁÁÁÁÁÁ–
ÁÁÁÁÁÁÁÁ1.2
ÁÁÁÁÁÁÁÁ–
ÁÁÁÁÁÁÁÁmVrmsRXI Shorted to Gnd via 10 µF
ÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁ
Confidence Level During DTMF Dialing ÁÁÁÁÁÁÁÁÁÁ
150 ÁÁÁÁÁÁÁÁ
200 ÁÁÁÁÁÁÁÁ
250 ÁÁÁÁÁÁÁÁ
mVrmsVMF = 7.5 mVrms MUT = Low
ÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁ
Available Peak Current from LSO ÁÁÁÁÁÁÁÁÁÁ
110 ÁÁÁÁÁÁÁÁ
– ÁÁÁÁÁÁÁÁ
– ÁÁÁÁÁÁÁÁ
mApeak
ÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁOutput Capability into 25 Ω ÁÁÁÁÁ1.8 ÁÁÁÁ– ÁÁÁÁ– ÁÁÁÁVppTHD ≤2%, VLSI = 55 mVrmsÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁ
ÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁOutput Capability into 25 Ω ÁÁÁÁÁ
ÁÁÁÁÁ2.7ÁÁÁÁÁÁÁÁ
–ÁÁÁÁÁÁÁÁ
–ÁÁÁÁÁÁÁÁ
VppTHD ≤2%, VLS = 5.0 V, VLSI = 90 mVrms
ÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁ
Gain Reduction in Mute Condition ÁÁÁÁÁÁÁÁÁÁ
60 ÁÁÁÁÁÁÁÁ
– ÁÁÁÁÁÁÁÁ
– ÁÁÁÁÁÁÁÁ
dBLSM = LowÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁ
ÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁRx CHANNEL PEAK–TO–PEAK LIMITERÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁ
ÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁPeak–to–Peak Limiter Attack Time
ÁÁÁÁÁÁÁÁÁÁ
–ÁÁÁÁÁÁÁÁ
–ÁÁÁÁÁÁÁÁ
5.0ÁÁÁÁÁÁÁÁ
msVLSI Jumps from 40 mVrms to 120 mVrms
ÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁ
Peak–to–Peak Limiter Release Time ÁÁÁÁÁÁÁÁÁÁ
– ÁÁÁÁÁÁÁÁ
300 ÁÁÁÁÁÁÁÁ
– ÁÁÁÁÁÁÁÁ
msVLSI Jumps from 120 mVrms to 40 mVrmsÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁ
ÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁTHD at 10 dB OverdriveÁÁÁÁÁÁÁÁÁÁ–
ÁÁÁÁÁÁÁÁ–
ÁÁÁÁÁÁÁÁ7.0
ÁÁÁÁÁÁÁÁ%VLSI = 120 mVrms
ÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁ
Peak–to–Peak Limiter Disable Threshold at PPL ÁÁÁÁÁÁÁÁÁÁ
– ÁÁÁÁÁÁÁÁ
– ÁÁÁÁÁÁÁÁ
0.1 ÁÁÁÁÁÁÁÁ
V
ÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁ
AUTOMATIC GAIN CONTROL
ÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁ
Gain Reduction in Transmit and Receive Channel with Respect to Iline = 18 mA ÁÁÁÁÁÁÁÁÁÁ
4.5 ÁÁÁÁÁÁÁÁ
6.0 ÁÁÁÁÁÁÁÁ
7.5 ÁÁÁÁÁÁÁÁ
dBIline = 70 mAÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁ
ÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁ
Gain Variation in Transmit and Receive Channel with Respect to Iline =18 mA withAGC Disabled (AGC to VDD)
ÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁ
–ÁÁÁÁÁÁÁÁÁÁÁÁ
–ÁÁÁÁÁÁÁÁÁÁÁÁ
1.5ÁÁÁÁÁÁÁÁÁÁÁÁ
dB
ÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁ
Highest Line Current for Maximum Gain ÁÁÁÁÁÁÁÁÁÁ
– ÁÁÁÁÁÁÁÁ
20 ÁÁÁÁÁÁÁÁ
– ÁÁÁÁÁÁÁÁ
mAÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁ
Lowest Line Current for Minimum Gain ÁÁÁÁÁÁÁÁÁÁ
– ÁÁÁÁÁÁÁÁ
50 ÁÁÁÁÁÁÁÁ
– ÁÁÁÁÁÁÁÁ
mAÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁ
BALANCE RETURN LOSSÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁ
Balance Return Loss with Respect to 600 Ω ÁÁÁÁÁÁÁÁÁÁ
20 ÁÁÁÁÁÁÁÁ
– ÁÁÁÁÁÁÁÁ
– ÁÁÁÁÁÁÁÁ
dB
ÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁ
SIDETONE
ÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁ
Voltage Gain from VHM to VEAR ÁÁÁÁÁÁÁÁÁÁ
– ÁÁÁÁÁÁÁÁ
– ÁÁÁÁÁÁÁÁ
28 ÁÁÁÁÁÁÁÁ
dBS1 in Position 2ÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁ
ÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁLOGARITHMIC AMPLIFIERS AND ENVELOPE DETECTORSÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁVoltage Gain from RXI to RSA
ÁÁÁÁÁÁÁÁÁÁ18
ÁÁÁÁÁÁÁÁ20
ÁÁÁÁÁÁÁÁ22
ÁÁÁÁÁÁÁÁdBVRXI = 15 mVrms
ÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁ
Voltage Gain from BMI to TSA ÁÁÁÁÁÁÁÁÁÁ
17.5 ÁÁÁÁÁÁÁÁ
18.5 ÁÁÁÁÁÁÁÁ
19.5 ÁÁÁÁÁÁÁÁ
dBVBM = 0.5 mVrmsÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁ
ÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁDynamic Range of Logarithmic Compression from TSA to TSE and RSA to RSEÁÁÁÁÁÁÁÁÁÁ40
ÁÁÁÁÁÁÁÁ–
ÁÁÁÁÁÁÁÁ–
ÁÁÁÁÁÁÁÁdB
ITSA and IRSA from 2.5 µA to 250 µAÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁ
Envelope Tracking Between TSE and RSE and Between TBN and RBN ÁÁÁÁÁÁÁÁÁÁ
– ÁÁÁÁÁÁÁÁ
±3.0 ÁÁÁÁÁÁÁÁ
– ÁÁÁÁÁÁÁÁ
dBÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁ
Maximum Source Current from TSE or RSE ÁÁÁÁÁÁÁÁÁÁ
0.3 ÁÁÁÁÁÁÁÁ
0.4 ÁÁÁÁÁÁÁÁ
0.5 ÁÁÁÁÁÁÁÁ
µA
NOTE: 2. Corresponding to –0.6 dB gain from the line to output RLS in the typical application.
Fre
esc
ale
Se
mic
on
du
cto
r, I
Freescale Semiconductor, Inc.
For More Information On This Product, Go to: www.freescale.com
nc
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MC33215
6 MOTOROLA ANALOG IC DEVICE DATA
ELECTRICAL CHARACTERISTICS (continued) (All parameters are specified at T = 25°C, Iline = 18 mA, VLS = 2.9 V, f = 1000 Hz,PRS = high, MUT = high, SPS = low, LSM = high, test figure in Figure 17 with S1 in position 1, unless otherwise stated.)
Characteristic UnitMaxTypMin
ÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁ
LOGARITHMIC AMPLIFIERS AND ENVELOPE DETECTORS
ÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁ
Maximum Sink Current into TSE or RSE ÁÁÁÁÁÁÁÁÁÁ
100 ÁÁÁÁÁÁÁÁ
– ÁÁÁÁÁÁÁÁ
– ÁÁÁÁÁÁÁÁ
µA
ÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁ
Maximum Sink Current into TBN and RBN ÁÁÁÁÁÁÁÁÁÁ
0.7 ÁÁÁÁÁÁÁÁ
1.0 ÁÁÁÁÁÁÁÁ
1.3 ÁÁÁÁÁÁÁÁ
µA
ÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁ
Maximum Source Current from TBN or RBN ÁÁÁÁÁÁÁÁÁÁ
100 ÁÁÁÁÁÁÁÁ
– ÁÁÁÁÁÁÁÁ
– ÁÁÁÁÁÁÁÁ
µA
ÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁ
Dial Tone Detector Threshold at Vline ÁÁÁÁÁÁÁÁÁÁ
– ÁÁÁÁÁÁÁÁ
20 ÁÁÁÁÁÁÁÁ
– ÁÁÁÁÁÁÁÁ
mVrms
ÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁ
Speech Noise Threshold Both Channels ÁÁÁÁÁÁÁÁÁÁ
– ÁÁÁÁÁÁÁÁ
4.5 ÁÁÁÁÁÁÁÁ
– ÁÁÁÁÁÁÁÁ
dB
ÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁ
ATTENUATOR CONTROL
ÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁ
Switching Depth ÁÁÁÁÁÁÁÁÁÁ
46 ÁÁÁÁÁÁÁÁ
50 ÁÁÁÁÁÁÁÁ
54 ÁÁÁÁÁÁÁÁ
dB
ÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁ
Adjustable Range for Switching Depth ÁÁÁÁÁÁÁÁÁÁ
24 ÁÁÁÁÁÁÁÁ
– ÁÁÁÁÁÁÁÁ
60 ÁÁÁÁÁÁÁÁ
dB
ÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁ
Gain Variation in Idle Mode for Both Channels ÁÁÁÁÁÁÁÁÁÁ
– ÁÁÁÁÁÁÁÁ
25 ÁÁÁÁÁÁÁÁ
– ÁÁÁÁÁÁÁÁ
dB
ÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁ
Current Sourced from SWT ÁÁÁÁÁÁÁÁÁÁ
7.0 ÁÁÁÁÁÁÁÁ
10 ÁÁÁÁÁÁÁÁ
13 ÁÁÁÁÁÁÁÁ
µATx ModeÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁ
ÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁCurrent Sunk into SWT
ÁÁÁÁÁÁÁÁÁÁ
7.0ÁÁÁÁÁÁÁÁ
10ÁÁÁÁÁÁÁÁ
13ÁÁÁÁÁÁÁÁ
µARx Mode
PIN FUNCTION DESCRIPTION
Pin
N D i iSDIP–42 TQFP–52 Name Description
ÁÁÁÁÁÁÁÁ
1 ÁÁÁÁÁÁÁÁ
47 ÁÁÁÁÁÁÁÁÁÁ
VCC ÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁ
Supply Output for Loudspeaker Amplifier and Peripherals
ÁÁÁÁÁÁÁÁ
2 ÁÁÁÁÁÁÁÁ
48 ÁÁÁÁÁÁÁÁÁÁ
VLN ÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁ
Line Connection Input
ÁÁÁÁÁÁÁÁ
3 ÁÁÁÁÁÁÁÁ
49 ÁÁÁÁÁÁÁÁÁÁ
VHF ÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁ
Supply Output for Speakerphone Section and Base Microphone
ÁÁÁÁÁÁÁÁ
4 ÁÁÁÁÁÁÁÁ
50 ÁÁÁÁÁÁÁÁÁÁ
VMC ÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁ
Supply Output for Handset Microphone
ÁÁÁÁÁÁÁÁ
– ÁÁÁÁÁÁÁÁ
51 ÁÁÁÁÁÁÁÁÁÁ
N/C ÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁ
Not Connected
ÁÁÁÁÁÁÁÁ
– ÁÁÁÁÁÁÁÁ
52 ÁÁÁÁÁÁÁÁÁÁ
N/C ÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁ
Not Connected
ÁÁÁÁÁÁÁÁ
5 ÁÁÁÁÁÁÁÁ
1 ÁÁÁÁÁÁÁÁÁÁ
SLB ÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁ
SLP Buffered Output
ÁÁÁÁÁÁÁÁ
6 ÁÁÁÁÁÁÁÁ
2 ÁÁÁÁÁÁÁÁÁÁ
REG ÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁ
Regulation of Line Voltage Adjustment
ÁÁÁÁÁÁÁÁ
7 ÁÁÁÁÁÁÁÁ
3 ÁÁÁÁÁÁÁÁÁÁ
SLP ÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁ
DC Slope Adjustment
ÁÁÁÁÁÁÁÁ
8 ÁÁÁÁÁÁÁÁ
4 ÁÁÁÁÁÁÁÁÁÁ
MFI ÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁ
DTMF Input
ÁÁÁÁÁÁÁÁ
9 ÁÁÁÁÁÁÁÁ
5 ÁÁÁÁÁÁÁÁÁÁ
HM1 ÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁ
Handset Microphone Input 1
ÁÁÁÁÁÁÁÁ
10 ÁÁÁÁÁÁÁÁ
6 ÁÁÁÁÁÁÁÁÁÁ
HM2 ÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁ
Handset Microphone Input 2
ÁÁÁÁÁÁÁÁ
11 ÁÁÁÁÁÁÁÁ
7 ÁÁÁÁÁÁÁÁÁÁ
BM2 ÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁ
Base Microphone Input 2
ÁÁÁÁÁÁÁÁ
12 ÁÁÁÁÁÁÁÁ
8 ÁÁÁÁÁÁÁÁÁÁ
BM1 ÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁ
Base Microphone Input 1
ÁÁÁÁÁÁÁÁ
13 ÁÁÁÁÁÁÁÁ
9 ÁÁÁÁÁÁÁÁÁÁ
VDD ÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁ
Supply Input for Speech Part
ÁÁÁÁÁÁÁÁ
14 ÁÁÁÁÁÁÁÁ
10 ÁÁÁÁÁÁÁÁÁÁ
TSA ÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁ
Transmit Sensitivity Adjustment
ÁÁÁÁÁÁÁÁ
15 ÁÁÁÁÁÁÁÁ
11 ÁÁÁÁÁÁÁÁÁÁ
TSE ÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁ
Transmit Signal Envelope Timing Adjustment
ÁÁÁÁÁÁÁÁ
16 ÁÁÁÁÁÁÁÁ
12 ÁÁÁÁÁÁÁÁÁÁ
TBN ÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁ
Transmit Background Noise Envelope Timing Adjustment
17 13 MUT Transmit and Receive Mute Input
ÁÁÁÁÁÁÁÁ
– ÁÁÁÁÁÁÁÁ
14 ÁÁÁÁÁÁÁÁÁÁ
N/C ÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁ
Not Connected
ÁÁÁÁÁÁÁÁ
– ÁÁÁÁÁÁÁÁ
15 ÁÁÁÁÁÁÁÁÁÁ
N/C ÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁ
Not Connected
ÁÁÁÁÁÁÁÁ
18 ÁÁÁÁÁÁÁÁ
16 ÁÁÁÁÁÁÁÁÁÁ
SPS ÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁ
Speakerphone Select Input
19 17 PRS Privacy Switch Input
ÁÁÁÁÁÁÁÁ
20 ÁÁÁÁÁÁÁÁ
18 ÁÁÁÁÁÁÁÁÁÁ
SWT ÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁ
Switch–Over Timing Adjustment
21 19 LSM Loudspeaker Mute Input
Fre
esc
ale
Se
mic
on
du
cto
r, I
Freescale Semiconductor, Inc.
For More Information On This Product, Go to: www.freescale.com
nc
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MC33215
7MOTOROLA ANALOG IC DEVICE DATA
PIN FUNCTION DESCRIPTION (continued)
Pin
DescriptionNameSDIP–42 DescriptionNameTQFP–52ÁÁÁÁÁÁÁÁ
–ÁÁÁÁÁÁÁÁ
20ÁÁÁÁÁÁÁÁÁÁ
N/CÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁ
Not ConnectedÁÁÁÁÁÁÁÁ
22ÁÁÁÁÁÁÁÁ
21ÁÁÁÁÁÁÁÁÁÁ
RXSÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁ
Receive Amplifier StabilityÁÁÁÁÁÁÁÁ
23ÁÁÁÁÁÁÁÁ
22ÁÁÁÁÁÁÁÁÁÁ
RXOÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁ
Receive Amplifier OutputÁÁÁÁÁÁÁÁ
24ÁÁÁÁÁÁÁÁ
23ÁÁÁÁÁÁÁÁÁÁ
GRXÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁ
Earpiece Amplifier Feedback InputÁÁÁÁÁÁÁÁ
25ÁÁÁÁÁÁÁÁ
24ÁÁÁÁÁÁÁÁÁÁ
RXIÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁ
Receive Amplifier InputÁÁÁÁÁÁÁÁ
–ÁÁÁÁÁÁÁÁ
25ÁÁÁÁÁÁÁÁÁÁ
N/CÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁ
Not ConnectedÁÁÁÁÁÁÁÁ
–ÁÁÁÁÁÁÁÁ
26ÁÁÁÁÁÁÁÁÁÁ
N/CÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁ
Not ConnectedÁÁÁÁÁÁÁÁ
26ÁÁÁÁÁÁÁÁ
27ÁÁÁÁÁÁÁÁÁÁ
RBNÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁ
Receive Background Noise Envelope Timing AdjustmentÁÁÁÁÁÁÁÁ
27ÁÁÁÁÁÁÁÁ
28ÁÁÁÁÁÁÁÁÁÁ
RSEÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁ
Receive Signal Envelope Timing AdjustmentÁÁÁÁÁÁÁÁ
28ÁÁÁÁÁÁÁÁ
29ÁÁÁÁÁÁÁÁÁÁ
RSAÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁ
Receive Sensitivity AdjustmentÁÁÁÁÁÁÁÁ
29ÁÁÁÁÁÁÁÁ
30ÁÁÁÁÁÁÁÁÁÁ
RLSÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁ
Receive Output for Loudspeaker AmplifierÁÁÁÁÁÁÁÁ
30ÁÁÁÁÁÁÁÁ
31ÁÁÁÁÁÁÁÁÁÁ
GndÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁ
Small Signal GroundÁÁÁÁÁÁÁÁ
31ÁÁÁÁÁÁÁÁ
32ÁÁÁÁÁÁÁÁÁÁ
AGCÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁ
Line Length AGC AdjustmentÁÁÁÁÁÁÁÁ
32ÁÁÁÁÁÁÁÁ
33ÁÁÁÁÁÁÁÁÁÁ
REFÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁ
Reference Current SetÁÁÁÁÁÁÁÁ
33ÁÁÁÁÁÁÁÁ
34ÁÁÁÁÁÁÁÁÁÁ
SWDÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁ
Switching Depth Adjustment for HandsfreeÁÁÁÁÁÁÁÁ
34ÁÁÁÁÁÁÁÁ
35ÁÁÁÁÁÁÁÁÁÁ
VOLÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁ
Volume Control AdjustmentÁÁÁÁÁÁÁÁ
35ÁÁÁÁÁÁÁÁ
36ÁÁÁÁÁÁÁÁÁÁ
LSIÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁ
Loudspeaker Amplifier InputÁÁÁÁÁÁÁÁ
36ÁÁÁÁÁÁÁÁ
37ÁÁÁÁÁÁÁÁÁÁ
PPLÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁ
Peak–to–Peak Limiter Timing AdjustmentÁÁÁÁÁÁÁÁ
37ÁÁÁÁÁÁÁÁ
38ÁÁÁÁÁÁÁÁÁÁ
BVOÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁ
Bias Voltage for Loudspeaker Amplifier OutputÁÁÁÁÁÁÁÁ
38ÁÁÁÁÁÁÁÁ
39ÁÁÁÁÁÁÁÁÁÁ
LSFÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁ
Loudspeaker Amplifier Feedback InputÁÁÁÁÁÁÁÁ
–ÁÁÁÁÁÁÁÁ
40ÁÁÁÁÁÁÁÁÁÁ
N/CÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁ
Not ConnectedÁÁÁÁÁÁÁÁ
–ÁÁÁÁÁÁÁÁ
41ÁÁÁÁÁÁÁÁÁÁ
N/CÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁ
Not ConnectedÁÁÁÁÁÁÁÁ
39ÁÁÁÁÁÁÁÁ
42ÁÁÁÁÁÁÁÁÁÁ
LSBÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁ
Loudspeaker Amplifier Bootstrap OutputÁÁÁÁÁÁÁÁ
40ÁÁÁÁÁÁÁÁ
43ÁÁÁÁÁÁÁÁÁÁ
VLSÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁ
Supply Input for Loudspeaker AmplifierÁÁÁÁÁÁÁÁ
41ÁÁÁÁÁÁÁÁ
44ÁÁÁÁÁÁÁÁÁÁ
LSOÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁ
Loudspeaker Amplifier OutputÁÁÁÁÁÁÁÁ
42ÁÁÁÁÁÁÁÁ
45ÁÁÁÁÁÁÁÁÁÁ
PGDÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁ
Power GroundÁÁÁÁÁÁÁÁ
–ÁÁÁÁÁÁÁÁ
46ÁÁÁÁÁÁÁÁÁÁ
N/CÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁ
Not Connected
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MC33215
8 MOTOROLA ANALOG IC DEVICE DATA
DESCRIPTION OF THE CIRCUIT
Based on the typical application circuit as given inFigure 18, the MC33215 will be described in three parts: linedriver and supplies, handset operation, and handsfreeoperation. The data used refer to typical data of thecharacteristics.
LINE DRIVER AND SUPPLIESThe line driver and supply part performs the ac and dc
telephone line termination and provides the necessarysupply points.
AC Set ImpedanceThe ac set impedance of the telephone as created by the
line driver and its external components can be approximatedwith the equivalent circuit shown in Figure 2.
Figure 2. Equivalent of the AC impedance
Inductor � RREG1 x CREG xRSLP
11
Slope �RSLP
11x �1� RREG1
RREG2�
CVLN10 n
CVDD100 µ
ZVDD620 Zbal
RSLB2.2 k
RREG∞
RREG1360 k
CREG220 n Slope
Inductor
With the component values of the typical application, theinductor calculates as 1.6 H. Therefore, in the audio range of300 Hz to 3400 Hz, the set impedance is mainly determinedby ZVDD. As a demonstration, the impedance matching orBalance Return Loss BRL is shown in Figure 3.
100
40
BRL
(dB)
f, FREQUENCY (Hz)
Figure 3. Balance Return Loss
35
30
25
20
15
10
5.0
01000 10000
The influence of the frequency dependent parasiticcomponents is seen for the lower frequencies (Inductor) andthe higher frequencies (CVLN) by a decreasing BRL value.
DC Set ImpedanceThe line current flowing towards the MC33215 application
is partly consumed by the circuitry connected to VDD whilethe rest flows into Pin VLN. At Pin VLN, the current is split up
into a small part for biasing the internal line drive transistorand into a large part for supplying the speakerphone. Theratio between these two currents is fixed to 1:10. The dc setimpedance or dc setting of the telephone as created by theline driver and its external components can be approximatedwith the equivalent of a zener voltage plus a series resistoraccording to:
Vzener � 0.2 x �1� RREG1RREG2�� �10 µA x RREG1�ILN � Iline – IVDD
Rslope �RSLP
11x �1� RREG1
RREG2�
With:
VLN � Vzener��ILN x Rslope�
If RREG2 is not mounted, the term between the bracketsbecomes equal to 1.
With the values shown in the typical application and underthe assumption that IVDD = 1.0 mA, the above formulas canbe simplified to:
VLN � 3.8 V���Iline – 1.0 mA� x 20�� 3.8 V� �Iline x 20�
In the typical application this leads to a line voltage of 4.2 Vat 20 mA of line current with a slope of 20 Ω. Adding a 1.5 Vvoltage drop for the diode bridge and the interruptor, the dcvoltage at tip–ring will equal 5.7 V.
If the dc mask is to be adapted to a country specificrequirement, this can be done by adjusting the resistorsRREG1 and RREG2, as a result, the zener voltage and theslope are varied. It is not advised to change the resistor RSLPsince this changes many parameters. The influence of RREG1and RREG2 is shown in Figure 4.
Figure 4. Influence of R REG1 and RREG2 on the DC Mask
0
12
VLN
(V)
Iline (mA)
10
8.0
6.0
4.0
2.0
020 40 60 80 100
.
RREG1 = 470 kRREG2 = 220 k
RREG1 = 365 kRREG2 = 220 k
RREG1 = 470 kRREG2 = Infinite
RREG1 = 365 kRREG2 = Infinite
As can be seen in Figure 4, for low line currents below10 mA, the given dc mask relations are no longer valid. Thisis the result of an automatic decrease of the current drawn
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MC33215
9MOTOROLA ANALOG IC DEVICE DATA
from Pin REG by the internal circuit (the 10 µA term in theformulas). This built–in feature drops the line voltage andtherefore enables parallel operation.
The voltage over the line driver has to be limited to 12 V toprotect the device. A zener of 11 V at VLN is therefore themaximum advised.
VDD SupplyThe internal circuitry for the line driver and handset
interface is powered via VDD. This pin may also be used topower peripherals like a dialer or microcontroller. The voltageat VDD is not internally regulated and is a direct result of theline voltage setting and the current consumption at VDDinternally (IVDD) and externally (IPER). It follows that:
VDD � VLN –�IVDD� IPER� x Rset
For correct operation, it must be ensured that VDD isbiased at 1.8 V higher than SLP. This translates to amaximum allowable voltage drop across ZVDD ofVzener – 1.8 V. In the typical application, this results in amaximum allowable current consumption by the peripheralsof 2.0 mA.
VMC SupplyAt VMC, a stabilized voltage of 1.75 V is available for
powering the handset microphone. Due to this stabilizedsupply, microphones with a low supply rejection can be usedwhich reduces system costs. In order to support the paralleloperation of the telephone set, the voltage at VMC will bemaintained even at very low line currents down to 4.0 mA.
Under normal supply conditions of line currents of 20 mAand above, the supply VMC is able to deliver a guaranteedminimum of 1.0 mA. However, for lower line currents, thesupply capability of VMC will decrease.
Figure 5. VMC Under Different Microphone Loads
0
1.8
VMC
(V)
IVMC (mA)
1.7
1.6
1.5
1.4
1.3
1.2
1.1
1.00.2 0.4 0.6 0.8 1.0 1.2 1.4 1.6
Iline = 4.0 mA2.7 k VMC–VHF
Iline = 20 mA
Iline = 4.0 mA
If, during parallel operation, a high current is required fromVMC, a 2.7 k resistor between VMC and VHF can be applied.In Figure 5, the VMC voltage under different microphonecurrents, is shown.
VHF SupplyVHF is a stabilized supply which powers the internal
duplex controller part of the MC33215, and which is alsomeant to power the base microphone or other peripherals.The base microphone however, can also be connected toVMC, which is preferred in case of microphones with a poorsupply rejection. Another possibility is to create an additionalfilter at VHF, like is shown in the typical application. Thesupply capability of VHF is guaranteed as 2.0 mA for linecurrents of 20 mA and greater.
Since in parallel operation not enough line current isavailable to power a loudspeaker and thus having aspeakerphone working, the current internally supplied to VHFis cut around 10 mA of line current to save current for thehandset operated part. A small hysteresis is built in to avoidsystem oscillations.
When the current to VHF is cut, the voltage at VHF willdrop rapidly due to the internal consumption of 1.4 mA andthe consumption of the peripherals. When VHF drops below2.0 V, the device internally switches to the handset mode,neglecting the state of the speakerphone select Pin SPS.
In case an application contains a battery pack or if it ismains supplied, speakerphone operation becomes possibleunder all line current conditions. In order to avoid switch–overto handset operation below the 10 mA, VHF has to besupplied by this additional power source and preferably keptabove 2.4 V.
VCC SupplyAt VCC the major part of the line current is available for
powering the loudspeaker amplifier and peripheral circuitry.This supply pin should be looked at as a current source sincethe voltage on VCC is not stabilized and depends on theinstantaneous line voltage and the current to and consumedfrom VCC.
The maximum portion of the line current which is availableat VCC is given by the following relation:
IVCC ��1011
x �Iline – IVDD�� – IVMC – IVHF This formula is valid when the voltage drop from VLN to
VCC is sufficient for the current splitter to conduct all thiscurrent to VCC. When the drop is not sufficient, the currentsource saturates and the surplus of current is conducted tothe power ground PGD to avoid distortion in the line driver. Infact, when no current is drawn from VCC, the voltage at VCCwill increase until the current splitter is in balance. In Figure 6this behavior is depicted.
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MC33215
10 MOTOROLA ANALOG IC DEVICE DATA
A. Maximum Available Current at V CC
Figure 6. Available Current at V CC
0
100
Iline (mA)
0
3.5
CC
VLN
–V
(V
)
Iline (mA)
90
80
70
60
50
40
30
20
10
020 40 60 80 100
3.0
2.5
2.0
1.5
1.0
0.5
020 40 60 80 100
B. Voltage Drop to V CC
IVCC/lline (%)
IVCC(max) (mA)
VCC to VLS
IVCC at 98% ofIVCC(max) IVCC at 50% of
IVCC(max)
VCC Open
mA
AND
%
For instance, at a line current of 20 mA a maximum of15 mA of current is available at VCC. If all this current istaken, VCC will be 1.7 V below VLN. When not all this currentis drawn from VCC, but for instance only 1.0 mA for biasing ofthe loudspeaker amplifier, the voltage at VCC will be 1.2 Vbelow VLN. Although the measurements for Figure 6 aredone with RREG1 = 365 k, the results are also globally validfor other dc settings.
As can be seen from Figure 6, the voltage at VCC is limitedby the voltage at VLN minus 1.0 V. This means that thevoltage at VCC is limited by the external zener at VLN. If it isnecessary to limit the voltage at VCC in order to protectperipheral circuits, a zener from VCC to Gnd can be added. Ifthe supply of the loudspeaker VLS is also connected to VCC,it is advisable that VCC does not exceed 8.0 V.
The high efficiency of the VCC power supply contributesto a high loudspeaker output power at moderate linecurrents. More details on this can be found in the handsfreeoperation paragraph.
HANDSET OPERATIONDuring handset operation, the MC33215 performs the
basic telephone functions for the handset microphone andearpiece. It also enables DTMF transmission.
Handset Microphone AmplifierThe handset microphone is to be capacitively connected
to the circuit via the differential input HM1 and HM2. Themicrophone signal is amplified by the HMIC amplifier andmodulates the line current by the injection of the signal intothe line driver. This transfer from the microphone inputs to theline current is given as 15/(RSLP/11), which makes a totaltransmit voltage gain AHM from the handset microphoneinputs to the line of:
AHM �VlineVHM
� 15RSLP�11
xZline x ZsetZline � Zset
With the typical application and Zline = 600 Ω the transmitgain calculates as 47 dB.
In case an electret microphone is used, it can be suppliedfrom the stabilized microphone supply point VMC of 1.75 Vproperly biased with resistors RHM1 and RHM2. This allowsthe setmaker to use an electret microphone with poor supplyrejection to reduce total system costs. Since the transmit gainAHM is fixed by the advised RSLP = 220 Ω and the constraintsof set impedance and line impedance, the transmit gain is set
by adjusting the sensitivity of the handset microphone byadjusting the resistors RHM1 and RHM2. It is not advised toadjust the gain by including series resistors towards the PinsHM1 and HM2.
A high pass filter is introduced by the coupling capacitorsCHM1 and CHM2 in combination with the input impedance. Alow pass filter can be created by putting capacitors in parallelwith the resistors RHM1 and RHM2.
The transmit noise is measured as –72 dBmp with thehandset microphone inputs loaded with a capacitivelycoupled 200 Ω. In a real life application, the inputs will beloaded with a microphone powered by VMC. Although VMCis a stablized supply voltage, it will contain some noise whichcan be coupled to the handset microphone inputs, especiallywhen a microphone with a poor supply rejection is used. Anadditional RC filter on VMC can improve the noise figure, seealso the base microphone section.
Handset Earpiece AmplifierThe handset earpiece is to be capacitively connected to
the RXO output. Here, the receive signal is available which isamplified from the line via the sidetone network and the Rxand EAR amplifiers. The sidetone network attenuates thereceive signal from the line via the resistor divider composedof RSLB and Zbal, see also the sidetone section. Theattenuation in the typical application by this network equals24.6 dB. Then the signal from the sidetone network ispre–amplified by the amplifier Rx with a typical gain of 6.0 dB.This amplifier also performs the AGC and MUTE functions,see the related paragraphs. Finally, the signal is amplified bythe noninverting voltage amplifier EAR. The overall receivegain ARX from the line to the earpiece output then follows as:
ARX �VRXOVline
� AST x ARXI x �1� RRXORGRX� With: AST = Attenuation of the Sidetone Network
ARXI = Gain of the Pre–Amplifier RxFor the typical application an overall gain from the line to
the earpiece is close to 0 dB.The receive gain can be adjusted by adjusting the resistor
ratio RRXO over RGRX. However, RRXO also sets theconfidence tone level during dialing which leaves RGRX to bechosen freely. A high pass filter is introduced by the couplingcapacitor CRXI together with the input impedance of the input
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MC33215
11MOTOROLA ANALOG IC DEVICE DATA
RXI. A second high pass filtering is introduced by thecombination of CGRX and RGRX. A low pass filter is createdby CRXO and RRXO. The coupling capacitor at the outputRXO is not used for setting a high pass filter but merely for dcdecoupling.
In combination with dynamic ear capsules, the EARamplifier can become unstable due to the highly inductivecharacteristic of some of the capsules. To regain stability, a100 nF capacitor can be connected from RXS to Gnd inthose cases. An additional 10 nF at the RXI input, as shownin the typical application, improves the noise figure of thereceiver stage.
Sidetone CancellationThe line driver and the receiver amplifier of the MC33215
are tied up in a bridge configuration as depicted in Figure 7.This bridge configuration performs the so–called hybridfunction which, in the ideal case, prevents transmitted signalsfrom entering the receive channel.
Figure 7. Sidetone Bridge
VHM x 15
RSLP�11
VLN
Zline//Zset
SLP
RSLP/11
Gnd
Zbal
RSLB Gnd
RXIReceive
Transmit
As can be seen from Figure 7 by inspection, the receiverwill not pick up any transmit signal when the bridge is inbalance, that is to say when:
ZbalRSLB
�
Zline��ZsetRSLP�11
The sidetone suppression is normally measured in anacoustic way. The signal at the earpiece when applying asignal on the microphone is compared with the signal at theearpiece when applying a signal on the line. The suppressiontakes into account the transmit and receive gains set. In factthe sidetone suppression can be given as a purely electricalparameter given by the properties of the sidetone bridgeitself. For the MC33215, this so–called electrical sidetonesuppression ASTE can be given as:
ASTE � 1 –Zbal
RSLBx
RSLP�11
Zline��Zset
Values of –12 dB or better, thus ASTE < 0.25, can easily bereached in this way.
Automatic Gain ControlTo obtain more or less constant signal levels for transmit
and receive regardless of the telephone line length, both thetransmit and receive gain can be varied as a function of linecurrent when the AGC feature is used. The gain reduction asa function of line current, and thus line length, is depicted inFigure 8.
0
0
AGC
(dB)
Iline (mA)
Figure 8. Automatic Gain Control
–1.0
–2.0
–3.0
–4.0
–5.0
–6.010 20 30 40 50 60 70
RAGC = 20 k
RAGC = 30 k
For small line currents, and thus long lines, no gainreduction is applied and thus the transmit and receive gainsare at their maximum. For line currents higher than Istart, thegain is gradually reduced until a line current Istop is reached.This should be the equivalent of a very short line, and thegain reduction equals 6.0 dB. For higher line currents thegain is not reduced further. For the start and stop currents thefollowing relations are valid:
Istop �1
RSLP�11
Istart �1
RSLP�11–
20 µ x RAGCRSLP�11
For the typical application, where RAGC = 30 kΩ, the gainwill start to be reduced at Istart = 20 mA while reaching 6.0 dBof gain reduction at Istop = 50 mA. When AGC is connected toVDD, the AGC function is disabled leading to no gainreduction for any line current. This is also sometimes calledPABX mode.
The automatic gain control takes effect in the HMIC and Rxamplifiers as well as in the BMIC amplifier. In this way theAGC is also active in speakerphone mode, see the handsfreeoperation paragraph.
Privacy and DTMF ModeDuring handset operation a privacy and a DTMF mode can
be entered according the logic Table 1.
Table 1. Logic Table for Handset Mode
Logic Inputs
M d
Amplifiers
SPS MUT PRS Mode HMIC BMIC DTMF Rx RXatt EARÁÁÁÁÁÁÁÁ0
ÁÁÁÁÁÁ1ÁÁÁÁÁÁÁÁ1
ÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁHandset Normal
ÁÁÁÁÁÁÁÁOn
ÁÁÁÁÁÁOffÁÁÁÁÁÁÁÁOff
ÁÁÁÁÁÁOnÁÁÁÁÁÁÁÁOff
ÁÁÁÁÁÁOnÁÁÁÁ
ÁÁÁÁ0ÁÁÁÁÁÁ1ÁÁÁÁÁÁÁÁ0
ÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁHandset Privacy
ÁÁÁÁÁÁÁÁOff
ÁÁÁÁÁÁOffÁÁÁÁÁÁÁÁOn
ÁÁÁÁÁÁOnÁÁÁÁÁÁÁÁOff
ÁÁÁÁÁÁOnÁÁÁÁ
ÁÁÁÁ0ÁÁÁÁÁÁ0ÁÁÁÁÁÁÁÁX
ÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁHandset DTMF
ÁÁÁÁÁÁÁÁOff
ÁÁÁÁÁÁOffÁÁÁÁÁÁÁÁOn
ÁÁÁÁÁÁOffÁÁÁÁÁÁÁÁOff
ÁÁÁÁÁÁOn
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MC33215
12 MOTOROLA ANALOG IC DEVICE DATA
Table 2. Logic Table for Handsfree Mode
Logic Inputs
M d
Amplifiers
SPS MUT PRS Mode HMIC BMIC DTMF Rx RXatt EARÁÁÁÁÁÁÁÁ
1ÁÁÁÁÁÁ
1ÁÁÁÁÁÁÁÁ
1ÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁ
Handsfree NormalÁÁÁÁÁÁÁÁ
OffÁÁÁÁÁÁ
OnÁÁÁÁÁÁÁÁ
OffÁÁÁÁÁÁ
OnÁÁÁÁÁÁÁÁ
OnÁÁÁÁÁÁ
OffÁÁÁÁÁÁÁÁ
1ÁÁÁÁÁÁ
1ÁÁÁÁÁÁÁÁ
0ÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁ
Handsfree PrivacyÁÁÁÁÁÁÁÁ
OffÁÁÁÁÁÁ
OffÁÁÁÁÁÁÁÁ
OnÁÁÁÁÁÁ
OnÁÁÁÁÁÁÁÁ
OnÁÁÁÁÁÁ
OffÁÁÁÁÁÁÁÁ
1ÁÁÁÁÁÁ
0ÁÁÁÁÁÁÁÁ
XÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁ
Handsfree DTMFÁÁÁÁÁÁÁÁ
OffÁÁÁÁÁÁ
OffÁÁÁÁÁÁÁÁ
OnÁÁÁÁÁÁ
OffÁÁÁÁÁÁÁÁ
OnÁÁÁÁÁÁ
Off
By applying a logic 0 to Pin MUT, the DTMF mode isentered where the DTMF amplifier is enabled and where theRx amplifier is muted. A DTMF signal can be sent to the linevia the MFI input for which the gain ADTMF is given as:
ADTMF �VlineVMFI
�3.75
RSLP�11x
Zline x ZsetZline� Zset
In the typical application, the gain equals 35 dB. TheDTMF gain can be controlled by a resistor divider at the inputMFI as shown in the typical application. The signal has to becapacitively coupled to the input via CMFI which creates ahigh pass filter with the input impedance. The line lengthAGC has no effect on the DTMF gains.
The signal applied to the MFI input is made audible at theearpiece output for confidence tone. The signal is internallyapplied to the GRX pin where it is amplified via the EARamplifier which is used as a current to voltage amplifier. Thegain is therefore proportional to the feedback resistor RRXO.For RRXO = 180 kΩ the gain equals 6.0 dB. The confidencetone is also audible at the loudspeaker output when theloudspeaker amplifier is activated, see speakerphoneoperation.
By applying a logic 0 to Pin PRS, the MC33215 entersprivacy mode. In this mode, both handset and handsfreemicrophone amplifiers are muted while the DTMF amplifier isenabled. Through the MFI input, a signal, for example musicon hold, can be sent to the line. In the same way, the MFIinput can also be used to couple in signals from, for instance,an answering machine.
HANDSFREE OPERATIONHandsfree operation, including DTMF and Privacy modes,
can be performed by making Pin SPS high according Table 2.The handset amplifiers will be switched off while the baseamplifiers will be activated. The MC33215 performs all thenecessary functions, such as signal monitoring andswitch–over, under supervision of the duplex controller.
With the MC33215 also a group listening–in applicationcan be built. For more information on this subject please referto application note AN1574.
Base Microphone AmplifierThe base microphone can be capacitively connected to
the circuit via the differential input BM1 and BM2. The setupis identical to the one for the handset microphone amplifier.The total transmit voltage gain ABM from the basemicrophone inputs to the line is:
ABM�VlineVBM
�37.5
RSLP�11x
Zline x ZsetZline� Zset
With the typical application and Zline = 600 Ω the transmitgain calculates as 55 dB.
The electret base microphone can be supplied directlyfrom VHF but it is advised to use an additional RC filter toobtain a stable supply point, as shown in the typicalapplication. The microphone can also be supplied by VMC.The transmit gain is set by adjusting the sensitivity of thebase microphone by adjusting the resistors RBM1 and RBM2.It is not advised to adjust the gain by including seriesresistors towards the Pins BM1 and BM2.
A high pass filter is introduced by the coupling capacitorsCBM1 and CBM2 in combination with the input impedance. Alow pass filter can be created by putting capacitors in parallelwith the resistors RBM1 and RBM2.
Loudspeaker AmplifierThe loudspeaker amplifier of the MC33215 has three major
benefits over most of the existing speakerphone loudspeakeramplifiers: it can be supplied and used in a telephone linepowered application but also stand alone, it has an all NPNbootstrap output stage which provides maximum outputswing under any supply condition, and it includes apeak–to–peak limiter to limit the distortion at the output.
The loudspeaker amplifier is powered at Pin VLS. Intelephone line powered applications, this pin should beconnected to VCC where most of the line current is available,see the VCC supply paragraph. In an application where anexternal power supply is used, VLS and thus the loudspeakeramplifier can be powered separately from the rest of thecircuit. The amplifier is grounded to PGD, which is the circuitspower ground shared by both the loudspeaker amplifier andthe current splitter of the VCC supply. Half the supply voltageof VLS is at BVO, filtered with a capacitor to VLS. Thisvoltage is used as the reference for the output amplifier.
The receive signal present at RLS can be capacitivelycoupled to LSI via the resistor RLSI. The overall gain fromRLS to LSO follows as:
ALS �VLSOVRLS
� –RLSFRLSI
x 4.0
In the typical application this leads to a loudspeaker gainALS of 26 dB. The above formula follows from the fact that theoverall amplifier architecture from RLS to LSO can be lookedat as an inverting voltage amplifier with an internal currentgain from LSI to LSF of 4. The input LSI is a signal currentsumming node which allows other signals to be applied here.
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MC33215
13MOTOROLA ANALOG IC DEVICE DATA
Figure 9. Loudspeaker Output Stage
VLS
Loudspeaker
CLSO
LSB
LSO
PGD
T2
T1
1.5 VLS
VLS
0.5 VLS
VLS
0.5 VLS
0
0.5 VLS
0
–0.5 VLS
VLS
Figure 10. Loudspeaker Amplifier Output Power with External Supply
2.0
140
PLS
P (m
W)
VLS (V)
2.0
300
RLSP = 25 Ω
RLSP = 50 Ω
RLSP = 25 Ω
RLSP = 50 ΩPLS
P (m
W)
VLS (V)
120 250
100200
80150
60
100
20 50
0 03.0 4.0 3.05.0 4.06.0 5.07.0 6.08.0 7.0 8.0
40
A. Peak–to–Peak Limiter Active B. Peak–to–Peak Limiter Disabled
The total gain from the telephone line to the loudspeakeroutput includes, besides the loudspeaker amplifier gain, alsothe attenuation of the sidetone network and the internal gainfrom RXI to RLS. When in receive mode, see under duplexcontroller, the gain from RXI to RLS is maximum and equals24 dB at maximum volume setting. The attenuation of thesidetone network in the typical application equals 24.6 dBwhich makes an overall gain from line to loudspeaker of25.4 dB. Due to the influence of the line length AGC on the Rxamplifier, the gain will be reduced for higher line currents.
The output stage of the MC33215 is a modified all NPNbootstrap stage which ensures maximum output swing underall supply conditions. The major advantage of this type ofoutput stage over a standard rail–to–rail output is the higherstability. The principle of the bootstrap output stage isexplained with the aid of Figure 9.
The output LSO is biased at half the supply VLS while thefiltering of the loudspeaker with the big capacitor CLSOrequires that LSB is biased at VLS. In fact, because of thefiltering, LSB is kept at VLS/2 above the LSO output even ifLSO contains an ac signal. This allows the output transistor
T2 to be supplied for output signals with positive excursionsup to VLS without distorting the output signal. The resultingac signal over the loudspeaker will equal the signal at LSO.As an indication of the high performance of this type ofamplifier, in Figure 10, the output power of the loudspeakeramplifier as a function of supply voltage is depicted for 25 Ωand 50 Ω loads with both the peak–to–peak limiter active anddisabled. As can be seen, in case the peak–to–peak limiter isdisabled, the output power is roughly increased with 6.0 dB,this at the cost of increased distortion levels up to 30%.
In a telephone line powered application, the loudspeakeramplifier output power is limited not only by the supplyvoltage but also by the telephone line current. This meansthat in telephones the use of 25 Ω or 50 Ω speakers ispreferred over the use of the cheaper 8.0 Ω types. Figure 11gives the output power into the loudspeaker for a linepowered application and two different dc settings with thepeak–to–peak limiter active. In case the peak–to–peak limiteris disabled the output power will be increased for the higherline currents up to 6.0 dB.
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MC33215
14 MOTOROLA ANALOG IC DEVICE DATA
0
100P L
SP (m
W)
Iline (mA)
RREG1 = 365 kRREG2 = 220 kRLSP = 25 Ω
Figure 11. Loudspeaker Amplifier OutputPower when Line Powered
RREG1 = 365 kRREG2 = 220 kRLSP = 50 Ω
RREG1 = 365 kRREG2 = InfiniteRLSP = 50 Ω
RREG1 = 365 kRREG2 = InfiniteRLSP = 25 Ω
20 40 60 80 100
90
80
70
60
50
40
30
20
10
0
The quality of the audio output of the loudspeaker amplifieris mainly determined by the distortion level. To keep highquality under difficult supply conditions, the MC33215incorporates a peak–to–peak limiter. The peak–to–peaklimiter will detect when the output stage gets close to itsmaximum output swing and will then reduce the gain from LSIto LSF. The attack and release of the limiter is regulated bythe CPPL capacitor. Figure 12 depicts the limiter’s attackbehavior with CPPL = 100 nF. The release time is given as3 x CPPL x RPPL. In the typical application this leads to arelease time of 300 ms.
Figure 12. Peak–to–Peak Limiter Dynamic Behavior
0
0.5
V/D
IV
t, TIME (ms)
VLSO
VPPL
Vin
1.0 2.0 3.0 4.0 5.0 6.0
Figure 12 clearly shows that due to the action of thepeak–to–peak limiter, the output swing and thus the outputpower is reduced with respect to the maximum possible asalready indicated in Figure 10. The peak–to–peak limiter canbe disabled by connecting the PPL pin to ground.
On top of the peak–to–peak limiter, the MC33215incorporates a supply limiter, which reduces the gain rapidlywhen the supply voltage VLS drops too much. This willavoid malfunctioning of the amplifier and unwantedoscillations. The voltage drop is detected via the BVO inputand for that reason the CBVO has to be connected to VLSand not to Gnd.
The amplifier can be activated by making Pin LSM high. Inthe typical application this pin is connected to SPS, whichactivates the loudspeaker amplifier automatically when thespeakerphone mode is entered. When LSM is made low, the
loudspeaker amplifier is muted which is needed for correcthandset operation.
The volume of the loudspeaker signal can be varied via apotentiometer at VOL. A fixed current of 10 µA is runningthrough the potentiometer and the resulting voltage at VOLis a measure for the gain reduction. The relation betweenthe voltage at VOL and the obtained gain reduction is givenin Figure 13.
0
0
dALS
P (d
B)
VVOL (mV), dALSP (dB)
Figure 13. Volume Reduction
100 200 300 400 500
–5.0
–10
–15
–20
–25
–35
–30
–40
It can be seen from Figure 13 that a linear variation ofRVOL will give a logarithmic gain reduction which adaptsbetter to the human ear than a linear gain reduction.
During DTMF dialing, see Table 2, a confidence tone isaudible at the loudspeaker of which the level is proportionalto the feedback resistor RLSF only. At RLSF = 180 kΩ the gainfrom MFI to LSO equals 28.5 dB.
Half Duplex ControllerTo avoid howling during speakerphone operation, a half
duplex controller is incorporated. By monitoring the signals inboth the transmit and receive channel the duplex controllerwill reduce the gain in the channel containing the smallestsignal. A typical gain reduction will be between 40 dB and52 dB depending on the setting, see below. In case of equalsignal levels or by detection of noise only, the circuit goes intoidle mode. In this mode the gain reduction in both channels ishalfway, leading to 20 dB to 26 dB of reduction.
In a speakerphone built around the MC33215, followingthe signal path from base microphone to the line and viasidetone, loudspeaker and acoustic coupling back to themicrophone, the loop gain can be expressed as a sum of thegains of the different stages. However, since the transmit andreceive gains are dependent on AGC and the sidetonesuppression is dependent on matching with the different lineswe are mostly interested by the maximum possible loop gainALOOP(max). It follows:
ALOOP(max) = ABMRX(max) + ARXBM(max) – ASWD (dB)
With: ABMRX(max) = Maximum gain from BM1 and BM2 toRXI as a function of line length AGC and lineimpedance matching
ARXBM(max) = Maximum gain from RXI to BM1 andBM2 as a function of line length AGC and acousticcoupling
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MC33215
15MOTOROLA ANALOG IC DEVICE DATA
ASWD = Switching depth as performed in theattenuators
To avoid howling, the maximum possible loop gain shouldbe below 0 dB and preferably below –10 dB for comfort. In apractical telephone design, both the ABMRX(max) and theARXBM(max) will be less than 20 dB thus a switching depth of50 dB will give a loop gain of less than –10 dB. An optimizedsidetone network is of high importance for handsfreeoperation. The better the network matches with thetelephone line the less local feedback and the smaller theswitching range can be.
The amount of gain reduction ASWD obtained by theduplex controller is set via resistor RSWD according:
ASWD � 20 log�3.6 x RSWD
RREF�
2
(dB)
In the typical application the gain reduction will be 50 dB.
To compare the transmit and receive signals with eachother, they have to be monitored. This is done by making asignal envelope and a background noise envelope via theCTSE, CTBN capacitors for the transmit channel and via theCRSE, CRBN capacitors for the receive channel. In Figure 14,a schematic behavior of the envelopes is depicted which isequal for both transmit and receive.
The voltage signal at the input is first transferred to acurrent via the sensitivity adjust network. Then this current isled through a diode which gives a logarithmic compression involtage. It is this voltage from which the signal envelope iscreated by means of asymmetric charge and discharge of thesignal envelope capacitor. The noise envelope voltage thenfollows in a similar way. Based on the envelope levels, theMC33215 will switch to transmit, receive or idle modefollowing Table 3. The fact that in receive mode the signal onthe base microphone is greater than it is in case of transmit
mode, due to the coupling of the high loudspeaker signal, isautomatically taken into account.
In the table, two particulars can be found. At first, the setwill go to idle mode if the signals are not at least 4.5 dBgreater then the noise floor, which calculates as a 13 mVvoltage difference in envelopes. This avoids continuousswitching over between the modes under slight variations ofthe background noise due to, for instance, typing on akeyboard. Second, a dial tone detector threshold isimplemented to avoid that the set goes to idle mode inpresence of a continuous strong receive signal like a dialtone. The dial tone detector threshold is proportional to theRRSA resistor. In the typical application with RRSA = 3.3 kΩ,the threshold is at 1.26 mVrms at the input RXI or 20 mVrmsat the line. Line length AGC is of influence on the dial tonedetector threshold, increasing the level depending on the linecurrent with a maximum of 6.0 dB.
In order to perform a correct comparison between thesignal strengths, the sensitivity of the envelope detectors canbe adjusted via the resistors connected to TSA and RSA.Based on the above, and on the fact that there is an effectivegain of 20 dB in the transmit monitor, it can be derived that forstable operation the following two relations are valid:
20 log�RTSA� � 20 log�RRSA� – ABMRX(max)� 20 (dB)
20 log�RTSA� � 20 log�RRSA� – ARXBM(max)– ASW� 20 (dB)
By measuring the gains and choosing the RRSA, the limitsfor RTSA follow. The choice for the sensitivity resistors is notcompletely free. The logarithmic compressors and theamplifier stages have a certain range of operation and, on thereceive side, the choice for RRSA is given by the desired dialtone detector threshold. Figure 15 indicates the availabledynamic range for the selected value of the sensitivityresistors.
Figure 14. Signal and Noise Envelopes
MicrophoneInput Signal
1.8 VInternal
TSA
RTSA
CTSA
TSECTSE CTBN
TBN
VHF VHF
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MC33215
16 MOTOROLA ANALOG IC DEVICE DATA
Table 3. Logic Table for Switch–Over
TSE > RSE TSE > TBN + 13 mV RSE > VDDT RSE > RBN + 13 mV ModeÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁ
1ÁÁÁÁÁÁÁÁÁÁÁÁÁÁ
1ÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁ
XÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁ
XÁÁÁÁÁÁÁÁÁÁÁÁÁÁ
TransmitÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁ
1ÁÁÁÁÁÁÁÁÁÁÁÁÁÁ
0ÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁ
XÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁ
XÁÁÁÁÁÁÁÁÁÁÁÁÁÁ
IdleÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁ
0ÁÁÁÁÁÁÁÁÁÁÁÁÁÁ
XÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁ
1ÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁ
XÁÁÁÁÁÁÁÁÁÁÁÁÁÁ
ReceiveÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁ
0ÁÁÁÁÁÁÁÁÁÁÁÁÁÁ
XÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁ
0ÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁ
1ÁÁÁÁÁÁÁÁÁÁÁÁÁÁ
ReceiveÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁ
0ÁÁÁÁÁÁÁÁÁÁÁÁÁÁ
XÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁ
0ÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁ
0ÁÁÁÁÁÁÁÁÁÁÁÁÁÁ
Idle
The resistors for the sensitivity setting have to be coupledcapacitively to the pins for dc decoupling, and also to createa high pass filter to suppress low frequent background noiseslike footsteps and 50 Hz.
The switch–over timing is performed by charging anddischarging the CSWT capacitor. The switch–over fromtransmit to receive or vice versa is fast, on the order ofmilliseconds, and is proportional to the value of CSWT. Theswitch–over to idle mode is slow, in the order of a fewseconds, and is proportional to the product of the values ofRSWT and CSWT. Figure 16 depicts a typical switch–overbehavior when applying transmit and receive stimuli.
The electrical characteristics and the behavior of theMC33215 are not the only factor in designing a handsfreespeakerphone. During the design the acoustics have to betaken into account from the beginning. The choice of thetransducers and the design of the cabinet are of greatinfluence on the speakerphone performance. Also, toachieve a proper handsfree operation, the fine tuning of thecomponents around the duplex controller have to be donewith the final choice of the cabinet and the transducers.
Figure 15. Compression Range of the Signal Monitors
100
100.0E–3
V RXI
(Vrm
s)
RRSA (Ω)
100
100.0E–3
RTSA (Ω)
A. Receive Monitor B. Transmit Monitor
Upper Limit ofCompression
Lower Limit ofCompression
Upper Limit ofCompression
Lower Limit ofCompression V B
M1(
Vrm
s)
1000 100010000 10000100000 100000
10.0E–310.0E–3
1.0E–3
1.0E–3100.0E–6
10.0E–6 100.0E–6
Dial ToneThreshold
Figure 16. Switch–Over Behavior
Receive
Transmit
SWT
VMC – 0.5
VMC + 0.5
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MC33215
17MOTOROLA ANALOG IC DEVICE DATA
VLSP
Figure 17. Test Circuit
Supply Supply1:10
VDD
VHM
VBM
VHF
VLS V
V
V
V
HM1
HM2
BM1
BM2
TSA
TSE
TBN
AGC
REF
SWD
VOL
RLS
BVO
VLS
LSB
LSO
PGD
LSF
Tx Log–Ampand
EnvelopeDetectors
AnalogControlBlock
PeakLimiter
AttenuatorControl
Tx Attenuator
Rx Attenuator Rx
EARLSP
BMIC
HMIC
VDD VLN
VRLS
GndVMC
VHF
VCC
SLB
SLP
MFI
SPS
MUT
PRS
LSM
SWT
RBN
RSE
RSA
RXI
RXO
GRX
RXSLSIPPL
Rx Log–Ampand Envelope
Detectors
LogicControlBlock
DTMF
Driver1x
MHM
MBM
MDF
MRX
MRA
MEAR
AGC
AGC
AGC
MRA
MHM
MBM MDF
MEAR
AGC
REG
MRX
RREG360 k
IlineVac
Vline
Zbal33 k
RSLB2.2 k
ZVDD620 600
0.2 V
CREG220 n
CVDD100 µ
CHM133 n
CHM233 nCBM133 n
CBM233 n
CTSA470 n
CTSE330 n
CTBN4.7 µ
RTSA2.2 k
RAGC30 kRREF20 k
RSWD100 k
RVOL47 k
CBVO220 n
CLSO47 µRLSO180 k
25
CLSI47 n
RLSI36 k
VLSI
RGRX24 k
RRXO180 k
CGRX47 n
VEAR
VRXI
CEAR10 µ
VHF
CRXS100 n
VMF
VSPS
VMUT
VPRS
VLSM
VSWT
CRXI47 n
RRSA3.3 k
CRSA470 n
CRSE330 n
CRBN4.7 µ
CMF147 n
RSLP220
CVCC470 µ
CVHF47 µ
CVMC10 µ
RPPL1.0 M
CPPL100 n
MC33215
S12
1
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MC33215
18 MOTOROLA ANALOG IC DEVICE DATA
Figure 18. Typical Application
Supply Supply1:10
VDD
VHF
HM1
HM2
BM1
BM2
TSA
TSE
TBN
AGC
REF
SWD
VOL
RLS
BVO
VLS
LSB
LSO
PGD
LSF
Tx Log–Ampand Envelope
Detectors
AnalogControlBlock
Peak Limiter
AttenuatorControl
Rx Attenuator Rx
EARLSP
BMIC
HMIC
VDD VLNGnd
VMC
VHF
VCC
SLB
SLP
MFI
SPS
MUT
PRS
LSM
SWT
RBN
RSE
RSA
RXI
RXO
GRX
RXSLSIPPL
Rx Log–Ampand Envelope
Detectors
Logic ControlBlock
DTMF
Driver1x
MHM
MBM
MDF
MRX
MRA
MEAR
AGC
AGC
AGC
MRA
MHM
MBM MDF
MEAR
AGC
REG
MRX
RREG1365 k Zbal
33 k
RSLB2.2 k
ZVDD620
0.2 V
CREG220 n
CVDD100 µ
CHM133 n
CHM233 n
CBM133 n
CBM233 n
CTSA1.0 µF
CTSE330 n
CTBN4.7 µ
RTSA470
RAGC30 k
RREF20 k
RSWD100 k
RVOL50 k
CBVO220 n
CLSO47 µ
RLSO180 k
RGRX24 k
RRXO180 k
CGRX47 n
150 Ω
CEAR10 µ
VHF
CRXS100 n
CRXI33 n
RRSA3.3 k
CRSA470 n
CRSE330 n
CRBN4.7 µ
CMF147 n
RSLP220
CVCC470 µ
CVHF47 µ
CVMC10 µ
RPPL1.0 M
CPPL100 n
MC33215VMC
VHF
VCC
25 Ω
CRLS33 n
RHM11.0 k
RBM21.0 k
RHM21.0 k
Dialer orMicrocontroller
Tx Attenuator
SpeakerphoneButton
PrivacyButton
Ring
Tip
T2
T1
Z110 V
VDD
HookSwitch
1
4
7
*
2
5
8
0
3
6
9
#
RBM11.0 k
CSWT100 n
1.0 k
10 µF
RSWT2.2 M
VMC
0.01
RLSI36 k
RREG2
10 n
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MC33215
19MOTOROLA ANALOG IC DEVICE DATA
FB SUFFIXPLASTIC PACKAGE
CASE 848B–04(TQFP–52)ISSUE C
OUTLINE DIMENSIONS
NOTES:1. DIMENSIONING AND TOLERANCING PER ANSI
Y14.5M, 1982.2. CONTROLLING DIMENSION: MILLIMETER.3. DATUM PLANE –H– IS LOCATED AT BOTTOM OF
LEAD AND IS COINCIDENT WITH THE LEAD WHERETHE LEAD EXITS THE PLASTIC BODY AT THEBOTTOM OF THE PARTING LINE.
4. DATUMS –A–, –B– AND –D– TO BE DETERMINED ATDATUM PLANE –H–.
5. DIMENSIONS S AND V TO BE DETERMINED ATSEATING PLANE –C–.
6. DIMENSIONS A AND B DO NOT INCLUDE MOLDPROTRUSION. ALLOWABLE PROTRUSION IS 0.25(0.010) PER SIDE. DIMENSIONS A AND B DOINCLUDE MOLD MISMATCH AND ARE DETERMINEDAT DATUM PLANE –H–.
7. DIMENSION D DOES NOT INCLUDE DAMBARPROTRUSION. ALLOWABLE DAMBAR PROTRUSIONSHALL BE 0.08 (0.003) TOTAL IN EXCESS OF THE DDIMENSION AT MAXIMUM MATERIAL CONDITION.DAMBAR CANNOT BE LOCATED ON THE LOWERRADIUS OR THE FOOT.
DETAIL A
L
39
40 26
27
1
52 14
13
L
–A–
B
V
SA–BM0.20 (0.008) D SH
A–B0.05 (0.002)
SA–BM0.20 (0.008) D SC
–D–B V
–B–
SA–
BM
0.20
(0.0
08)
DS
H
A–B
0.05
(0.0
02)
SA–
BM
0.20
(0.0
08)
DS
C
–H–
0.10 (0.004)–C– SEATING
PLANE
DATUMPLANE
MGH
EC M
�
�
DETAIL C
U�
Q�
XW
KT
R
DETAIL C
DIM MIN MAX MIN MAXINCHESMILLIMETERS
A 9.90 10.10 0.390 0.398B 9.90 10.10 0.390 0.398C 2.10 2.45 0.083 0.096D 0.22 0.38 0.009 0.015E 2.00 2.10 0.079 0.083F 0.22 0.33 0.009 0.013G 0.65 BSC 0.026 BSCH ––– 0.25 ––– 0.010J 0.13 0.23 0.005 0.009K 0.65 0.95 0.026 0.037L 7.80 REF 0.307 REFM 5 10 5 10 N 0.13 0.17 0.005 0.007Q 0 7 0 7 R 0.13 0.30 0.005 0.012S 12.95 13.45 0.510 0.530T 0.13 ––– 0.005 –––U 0 ––– 0 –––V 12.95 13.45 0.510 0.530W 0.35 0.45 0.014 0.018X 1.6 REF 0.063 REF
� � � �
� � � �
� �
B
B
DETAIL A
–A–, –B–, –D–
J N
D
F
BASE METAL
SECTION B–B
SA–BM0.02 (0.008) D SC
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Freescale Semiconductor, Inc.
For More Information On This Product, Go to: www.freescale.com
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MC33215
20 MOTOROLA ANALOG IC DEVICE DATA
B SUFFIXPLASTIC PACKAGE
CASE 858–01(SDIP–42)ISSUE O
OUTLINE DIMENSIONS
–A–
1 21
42 22
–B–
SEATINGPLANE
–T–
SAM0.25 (0.010) T SBM0.25 (0.010) T
L
H
MJ 42 PLD 42 PL
F GN
K
C
NOTES:1. DIMENSIONING AND TOLERANCING PER ANSI
Y14.5M, 1982.2. CONTROLLING DIMENSION: INCH.3. DIMENSION L TO CENTER OF LEAD WHEN
FORMED PARALLEL.4. DIMENSIONS A AND B DO NOT INCLUDE MOLD
FLASH. MAXIMUM MOLD FLASH 0.25 (0.010).
DIM MIN MAX MIN MAXMILLIMETERSINCHES
A 1.435 1.465 36.45 37.21B 0.540 0.560 13.72 14.22C 0.155 0.200 3.94 5.08D 0.014 0.022 0.36 0.56F 0.032 0.046 0.81 1.17G 0.070 BSC 1.778 BSCH 0.300 BSC 7.62 BSCJ 0.0