particle swarm optimization in the determination of the optimal bias current for noise performance...
TRANSCRIPT
Figure 8 shows the measured radiation patterns including the
copolarization and crosspolarization in the H-plane (y–z plane)
and E-plane (x–y plane). It can be seen that the radiation pat-
terns in both of y–z and x–y planes are nearly omnidirectional
for the two frequencies.
Figure 9 shows the measured and simulated maximum gain
of the proposed antenna and demonstrates a variation similar to
other PIFA antennas. As shown in Figure 9 for the WLAN/
WiMAX frequencies, the measured antenna gain agrees very
well with the simulated results.
4. CONCLUSIONS
In this article, a novel compact printed inverted-F antenna has
been proposed for simultaneously satisfying WLAN and WiMAX
applications. The fabricated antenna has the frequency band of
4.95 to over 5.91. The desired resonant frequencies are obtained
by adjusting the dimension of T-shaped notch. Also, to enhance
the impedance bandwidth characteristic, a rectangular slot is
inserted in the ground plane of the proposed antenna. Prototypes
of the proposed antenna have been constructed and studied exper-
imentally. The measured results showed good agreement with the
numerical prediction and good multiband operation.
ACKNOWLEDGMENT
The authors are thankful to Iran Telecommunication Research Cen-
ter (ITRC) for its financial support of the work.
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VC 2011 Wiley Periodicals, Inc.
PARTICLE SWARM OPTIMIZATION IN THEDETERMINATION OF THE OPTIMAL BIASCURRENT FOR NOISE PERFORMANCEOF GALLIUM NITRIDE HEMTS
Tyler Ross,1 Gabriel Cormier,1 Khelifa Hettak,2
and Rony E. Amaya21 Faculte d’ingenierie, Universite de Moncton, 57, avenueAntonine-Maillet, Moncton (N.-B), Canada E1A 3E9;Corresponding author: [email protected] Research Centre Canada, 3701 CarlingAvenue, P.O. Box 11490, Station H, Ottawa, ON, CanadaK2H 8S2
Received 1 June 2010
ABSTRACT: Gallium nitride has attracted a great deal of interestin recent years due to its power handling ability. In addition, its
noise performance is known to be good. In this letter, we presenta method for determining the bias current density needed to
obtain optimal noise figure for gallium nitride high-electronmobility transistors (HEMTs). Particle swarm optimization is usedto fit transistor S parameters to a model, enabling the calculation
of the transistor’s two-port noise parameters. This process isperformed for different bias points for different-sized transistors,
leading to the conclusion that a current density of 0.3 mA/lmyields the best minimum noise figure. VC 2011 Wiley Periodicals,
Inc. Microwave Opt Technol Lett 53:652–656, 2011; View this
article online at wileyonlinelibrary.com. DOI 10.1002/mop.25758
Key words: gallium nitride; noise figure; noise modeling; MMIC; lownoise amplifiers
1. INTRODUCTION
In the past few years, gallium nitride has attracted the interest
of microwave circuit designers. This is been principally due to
its high suitability for power amplifiers, including its perform-
ance at high temperatures, its good power handling capacity and
its high breakdown voltage [1, 2].
In addition to its suitability for high heat and high power
applications, previous studies have noted its high resistance to
ionizing radiation, which is much higher than the radiation re-
sistance of gallium arsenide circuits [3]. If a designer would like
to benefit from the advantages that gallium nitride offers, then
one obvious route is to consider its use in a complete integrated
circuit.
In this case, a proper understanding of the noise behavior of
the transistors in the gallium nitride process being considered
for use is required. Different authors have reported on the noise
of gallium nitride circuits and these types of transistors are
reported to have good noise performance (see [4, 5], for
example).
In this work, a predictive noise model was applied to
describe the noise of gallium nitride transistors. Specifically, the
relationship between the minimum noise figure, Fmin, and tran-
sistor bias current was sought. To identify this relationship,
measured device S parameters must be fitted to a small-signal
transistor model. To do so, particle swarm optimization, a global
search algorithm was used.
A previous study by Dickson et al. examined the noise de-
pendence on the current density of various CMOS transistors
having different dimensions, bias conditions, and gate lengths
[6]. In that study, the authors found that regardless of the bias
conditions, transistor dimensions, and fabrication process,
652 MICROWAVE AND OPTICAL TECHNOLOGY LETTERS / Vol. 53, No. 3, March 2011 DOI 10.1002/mop
optimal Fmin was obtained at 0.15 mA/lm. This letter deals
only with noise performance and will show that a similar
result holds for the gallium nitride high-electron mobility
transistors (HEMTs) used here, albeit at a current density of
0.3 mA/lm.
This letter is laid out as follows: section 2 presents the meth-
odology used in this study, section 3 presents the particle swarm
optimization algorithm used to determine the transistor’s small-
signal parameters, section 4 describes the gallium nitride devices
used for this study, and section 5 presents and discusses the
results obtained.
2. METHODOLOGY
Noise models for field-effect transistors, and specialized models
for MESFETs and HEMTs specifically, have been presented and
have been well-known for quite some time. In addition, in more
recent years, noise models for gallium nitride HEMTs in partic-
ular, have been demonstrated [5, 7]. These models typically
have some weaknesses, such as the incorporation of fitting pa-
rameters which must be determined from measurements and
which in some case have no physical origin, noise sources are
occasionally neglected (many gallium nitride devices have gate
leakage currents which becomes a relatively important noise
source [8]), and some models do not enable the determination of
the four noise parameters used in microwave circuit analysis
(Rn, Ropt, Xopt, and Fmin).
A model presented by Sanabria et al. meant for use with gal-
lium nitride HEMTs, does not exhibit these shortcomings [9].
This predictive model uses a typical, small-signal HEMT model
in addition to bias conditions (including gate current) and can
determine all four noise parameters. This model does not depend
on fitting parameters or require noise measurements. The HEMT
model parameters must be determined which could require
measurements, though only S parameters would be necessary,
simplifying the process.
The model presented in [9] was applied to several transistors,
to determine their noise parameters. To validate the results
obtained, noise measurements were taken and compared with
the model’s predictions for several transistors and operating
conditions.
The small-signal model parameters used in the noise calcu-
lations are determined by fitting transistor S parameters to a
13-element small-signal HEMT model, shown in Figure 1.
This model was used because the device parameters used to
calculate the noise parameters cannot be directly obtained
from the measurement-based large-signal model developed by
Gain Microwave to predict the behavior of the measured
devices [10].
Fitting of S parameter data to the small-signal model was
accomplished using particle swarm optimization, a global
search algorithm well-suited to this type of problem. Because
particle swarm optimization is not commonly used in micro-
wave circuit design, the algorithm is presented in the follow-
ing section.
3. PARTICLE SWARM OPTIMIZATION
Particle swarm optimization is a global search algorithm first
proposed Kennedy et al. [11]. This algorithm is based on swarm
intelligence, where a large population collectively seeks a solu-
tion. One example is a swarm of bees seeking flowers to
pollinate.
The behavior of a particle is determined jointly by the col-
lective experience of the swarm and its own ‘‘personal’’ experi-
ence. The particle will wander toward the space between where
it had the most success (the local best) and where the entire
swarm had the most success (the global best). Although the par-
ticle swarm optimization algorithm does use random processes,
it is usually much more effective than a simple random search.
The algorithm can be broken down into a series of individual
steps, shown in Figure 2, which will be discussed further.
3.1. Creation of the SwarmThe first step of the algorithm involves the creation of the
initial swarm of particles that will search for the optimal so-
lution. The particles are placed in an n-dimensional space,
where n is the number of variables in the problem. In the
case of fitting S parameter data to the model shown in Figure
Figure 1 Small-signal transistor model used to calculate noise
parameters
Figure 2 Flowchart illustrating the particle swarm optimization
algorithm
DOI 10.1002/mop MICROWAVE AND OPTICAL TECHNOLOGY LETTERS / Vol. 53, No. 3, March 2011 653
1, n would be 13. In this case, each particle is exploring a
13-dimensional space, each of the unknown variables corre-
sponding to one dimension.
The coordinates of each particle in the swarm are initialized
within a predetermined range specific to the problem. For exam-
ple, for the problem at hand, the transconductance gm of the
transistor is likely between 0 S and 4 S. The transconductances
of each particle will therefore fall inside these limits. Care must
be taken when selecting these limits: restricting the variable
space too much could lead to the optimal solution being
excluded, whereas a large distance between the two limits could
lead to convergence issues, requiring more particles and compu-
tational effort and time.
For the particle swarm optimization algorithm, the population
size is dependent on the problem. For the problem of fitting Sparameter data to a model, approximately eight particles per
variable appears to work well, leading to a swarm of 104
particles.
3.2. Evaluation of the Objective FunctionThe objective function determines the quality of a solution. In
fitting S parameters, the objective function measures the error
between the already-known S parameter data and the S parame-
ters of the small-signal model with parameters whose perform-
ance is to be evaluated. Equation (1) shows our objective func-
tion; it is based on the commonly used statistical measure of
goodness-of-fit for sum-of-squares minimization. In this equa-
tion, N is the number of (frequency) measurements, the sub-
scripts m and c indicate the measured and calculated values,
respectively, and e is the uncertainty on the S parameters. The
notation of the inner summation is simply to indicate that all
four S parameters are used in the evaluation of the objective
function.
v2 ¼ 1
4N
XNk¼1
XSi;j
ReðSi;jkm � Si;jkc Þ� �2þ ImðSi;jkm � Si;jkc Þ
� �2e
" #
(1)
The use of this biased objective function offers some
advantages over an unbiased objective function. First, it pro-
vides for weighting of the error between measurements and
model results, depending on the uncertainty of the measure-
ments (less reliable measurements are accorded less weight).
Second, it gives an indication of the error of the measure-
ments. When v2 � 1, the error is similar to the error of the
measured data, and the fit is good. If v2 >> 1, the error
between measurements and calculations is significantly differ-
ent from the uncertainty of the measurements. However, when
v2 >> 1, the uncertainty of the measurements may have
been overestimated.
3.3. Local and Global BestsThe local best of any given particle is found by comparing the cur-
rent value of the objective function with that particle’s previous
local best. If it is better, it will become the new local best. This
results in each particle having a limited ‘‘memory’’ of its past.
Similarly, the swarm as a whole keeps track of its global
best. The global best is the best of the individual particles’ local
bests, past or present.
3.4. Velocity and Position UpdatesOnce the local and global bests have been determined, they are
used to update the velocities of the particles. This is done to
guide each particle toward a stronger result. The velocity of par-
ticle k for the time step t þ 1 is given by
~vk½tþ 1� ¼ w~vk½t� þ c1~r1ðxg �~xk½t�Þ þ c2~r2ðxk �~xk½t�Þ; (2)
where ~v is the velocity of a particle, ~x is its position, and x sig-
nifies a best, whereas the subscript g indicates a global best and
the subscript k references the local particle. ~r1 and ~r2 are vectors
of random numbers with the number of elements of xk, in the
range (0,1). c1 and c2 decide how quickly the particle should
move toward its local best and the global best. Finally, w is the
inertia weight, a parameter that balances global and local explo-
ration of the search space [12].
Initial suggestions for these weights are w [ (0.9, 1.2) [12]
and c1 ¼ c2 ¼ 2 [11]. These values typically need to be hand-
tuned if they do not lead to convergence or if the algorithm con-
verges slowly.
Figure 3 Microphotograph of a wafer with the measured transistors.
The measured dimensions of the wafer are 1.2 mm � 0.76 mm. The
inset shows a 2 � 10 lm transistor (gate on right, drain on left, source
access on top and bottom)
Figure 4 Measured and modeled S11 and S21 for a 2 � 40 lm HEMT
654 MICROWAVE AND OPTICAL TECHNOLOGY LETTERS / Vol. 53, No. 3, March 2011 DOI 10.1002/mop
Lastly, the new position of each particle, k, is updated using
the following equation,
~xk½tþ 1� ¼~xk½t� þ~vk½tþ 1�: (3)
4. GALLIUM NITRIDE TRANSISTORS
Different gallium nitride devices were studied. The transistors
are AlGaN/GaN HEMTs, manufactured using the National
Research Council Canada’s gallium nitride foundry process, and
were supplied by Gain Microwave Corporation [10].
The AlGaN/GaN structure was grown on a semi-insulating,
500-lm-thick 4H-SiC substrate using ammonia molecular beam
epitaxy. Contact optical lithography was used to define transis-
tors having gate lengths of 0.8 lm. The devices have an ft of �15 GHz and an fmax of 45 GHz. All metal traces are 1-lm-thick
gold for this process. The fabrication process is more fully
described in [10]. Figure 3 shows a microphotograph of one of
the two identical wafers used for measurements.
As shown in Figure 3, the devices can be probed directly
using coplanar ground-signal-ground probes having a 100 lmpitch. The devices measured are all two-fingered transistors,
with gate finger widths of 10, 20, 40, 100, or 200 lm.
Noise measurements were taken from 3 to 6 GHz under vari-
ous bias conditions. The bias points were selected to provide the
best noise performance. This is typically just in the saturation
region of the I-V characteristic. For these gallium nitride devi-
ces, this usually occurs for drain voltages of � 5–7 V. The gate
voltage in this case was varied from �2 to �4 V, which yields
a fairly large range of drain current densities.
5. RESULTS AND DISCUSSION
The transistor S parameters were first measured on-wafer using
an Agilent E8361C PNA network analyzer. For noise measure-
ments, the transistors were probed using an Agilent N5242A
PNA-X network analyzer with a noise figure measurement sys-
tem. Ground-signal-ground probes with 100 lm pitch and short-
open-load-through de-embedding were used to remove the effect
of the measurement cables and probes.
Small-signal S parameters were measured first and compared
to a large-signal device model. As can be seen in Figure 4,
model simulations and measurements agree very well. Only S11and S21 are shown in this figure to avoid cluttering the image;
measurements of S12 and S22 also agree well with simulation
results.
The small-signal measurements show that the model is accu-
rate. However, it is difficult to extract accurate values for some
of the small-signal model parameters from this type of model.
For this reason, a 13-parameter small-signal model was fitted to
S parameters, to apply the predictive noise model described in
[9], using particle swarm optimization, as described in section 3.
Note that some of the parameters in the small-signal model vary
with bias, so this procedure must be repeated for each bias
point. Some of the parameters which do not vary with bias can
be held constant.
Noise parameters were calculated for several operating points
for each transistor. Figure 5 shows Fmin for the five devices, as
a function of drain current density. The drain voltage was set to
5 V in all cases. This places the transistors in their saturation
Figure 5 Minimum noise figure, Fmin, as a function of current density,
for transistors having different gate widths, at 5 GHz, and VD ¼ 5 V
Figure 6 Noise figure, F, for VG ¼ �2 V and VD ¼ 5 V, for the 2 �40 lm device, with a 50 X source impedance
Figure 7 Noise figure, F, calculated for VG ¼ �2 V and VD ¼ 5 V,
for the 2 � 40 lm device after fitting measured S parameters to a small-
signal HEMT model, with a 50 X source impedance
DOI 10.1002/mop MICROWAVE AND OPTICAL TECHNOLOGY LETTERS / Vol. 53, No. 3, March 2011 655
regions. The noise figures shown were determined for transistor
operation at 5 GHz.
The variability in the noise figure is due to the small-signal
transistor model not fitting the S parameters predictions of the
large-signal model. However, the error is fairly small, and the
tendencies of the noise figure as a function of current density
are clear.
As can be seen from Figure 5, the best Fmin is obtained for
current densities of � 0.3 mA/lm, even for transistors of differ-
ent sizes. This indicates that optimal noise performance can be
obtained from an amplifier if it is biased using a constant-cur-
rent configuration.
To validate the results of the model, noise figure measure-
ments were taken. The noise figure measured and simulated at
50 X for a 2 � 40 lm device is shown in Figure 6. These
curves fit quite well, indicating that the model accurately repre-
sents reality.
Instead of relying on a large-signal model to be able to deter-
mine the small-signal parameters and then calculate noise pa-
rameters, it is possible to simply extract the HEMTs small-sig-
nal parameters from the S parameter measurements. In this case,
any additional terminal resistance and inductance will be
included directly in the fitted parameters, which should lead to
improved accuracy of the noise predictions.
Figure 7 shows the result of this procedure. Again, it should
be noted that no noise figure measurements were included in
this fitting process; the noise figure is determined using only
measured scattering parameters. The fit is good and the models
used were able to accurately predict noise figure, lending more
confidence to the results of Figure 5.
6. CONCLUSIONS
This letter has shown the dependence of the optimal minimum
noise figure (Fmin) on the drain current density of gallium nitride
HEMTs. It was found that the best noise performance was
obtained for current densities of � 0.3 mA/lm. This result was
obtained by using particle swarm optimization to determine a
transistor’s small-signal parameters, which were then used to
predict the noise parameters.
This result is useful to those designing gallium nitride low-
noise amplifiers, who must attain the lowest possible noise fig-
ure. Because the best noise figure is found at a given current
density, an effort should be made when designing an amplifier
to use constant-current biasing. This ensures that an optimal
noise figure is obtained and will not be unnecessarily degraded
by foundry process variations and tolerances.
The results discussed in this letter are similar to previous
results regarding CMOS transistors, although the optimal cur-
rent density for noise figure is found to be twice the current
density required for CMOS transistors. Gallium arsenide
designers have also been aware of a similar rule, where 0.15
mA/lm, or � 0.2IDSS, has traditionally yielded optimal noise
performance. During our work, we have found that gallium
nitride devices work best at even higher drain current
densities.
ACKNOWLEDGMENTS
The authors express their appreciation to the Natural Sciences
and Engineering Research Council of Canada (NSERC) for
their financial support. The authors thank Agilent Technologies,
Inc., for the loan of measurement equipment. Finally, the
authors appreciate Gain Microwave Corporation having pro-
vided the gallium nitride transistors studied and presented in
this article.
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A NOVEL COMPACT DUAL-MODEBANDPASS FILTER
M. Keshvari and M. TayaraniDepartment of Electrical Engineering, Iran University of Scienceand Technology, Tehran, Iran; Corresponding author:[email protected]
Received 2 June 2010
ABSTRACT: Using slow-wave transmission line ring resonator and
square-patch element, a novel compact dual-mode microstrip bandpassfilter is developed in this article. A filter having a 3% bandwidth at 2
GHz is designed, fabricated, and measured. The design procedure isgiven, and the mode-splitting characteristic and impact of the patchelement on the performance of the filter is investigated. The proposed
656 MICROWAVE AND OPTICAL TECHNOLOGY LETTERS / Vol. 53, No. 3, March 2011 DOI 10.1002/mop