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TRANSCRIPT
Copyright Mark Rodwell, 2016
Mixers:
Reciprocity
N-path designs
Mark Rodwell, University of California, Santa Barbara
ece145c lecture notes
Copyright Mark Rodwell, 2016
Ideal mixing is multiplication
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Copyright Mark Rodwell, 2016
Mixing: learn to do the math efficiently
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Copyright Mark Rodwell, 2016
Mixing by time-dependent conductance
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Copyright Mark Rodwell, 2016
The LO drive should be big !
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Copyright Mark Rodwell, 2016
With big LO drive, mixer becomes a switch
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Copyright Mark Rodwell, 2016
Idealized (switch) double-balanced mixer
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Copyright Mark Rodwell, 2016
A Gilbert-cell mixer is an amplifier and a switch
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Copyright Mark Rodwell, 2016
Typical mixer presentation then moves to circuits:
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Copyright Mark Rodwell, 2016
Ideal switch-based mixer
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Copyright Mark Rodwell, 2016
What is our goal ?
min low havecan frequency,lower at operates amp IF :Note
IP3.receiver higher cost,Lower
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Copyright Mark Rodwell, 2016
Even ideal mixers have:
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Copyright Mark Rodwell, 2016
Image response→ interference, loss of SNR
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Copyright Mark Rodwell, 2016
But there is *a different* image response problem:
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Copyright Mark Rodwell, 2016
LO harmonics also produce images:
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Copyright Mark Rodwell, 2016
Ideally: eliminate spurious responses with filters
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Copyright Mark Rodwell, 2016
Real mixers are bilateral, not unilateral
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Copyright Mark Rodwell, 2016
Diode Double Balanced Mixer: Two-Port Representation
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Copyright Mark Rodwell, 2016
Bilateral mixing→ spurious RF responses
etc. ,2 @
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Copyright Mark Rodwell, 2016
Eliminating Noise from Image Response
frequency imageat power
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frequency imageat noise ~ :Filtering
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Copyright Mark Rodwell, 2016
System-Level Mixer Noise analysis
frequency imagefor gain mixer
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Citation: TUTORIAL 5594: System Noise-Figure Analysis for Modern Radio Receivers By: Charles Razzell,Maxim Integrated Products, Inc.
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Copyright Mark Rodwell, 2016
System-Level Mixer Noise analysis
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Copyright Mark Rodwell, 2016
System-Level Mixer Noise analysis
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Copyright Mark Rodwell, 2016
System-Level Mixer Noise analysis: another case
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Copyright Mark Rodwell, 2016
System-Level Mixer Noise analysis: Big Picture
model noiseMixer
model noiseReceiver
filtered. bet can' This
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responses image and harmonicmixer minimize try to:Clearly
Copyright Mark Rodwell, 2016
Eliminating Noise from Image Response
frequency imageat power
noise available zero provides Trap
response noise image and signal image
both suppressesmixer reject -Image
frequency signalat noise ~but
frequency imageat noise ~ :Filtering
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Copyright Mark Rodwell, 2016
N-path mixers: Motivation
Why use LNAs in superheterodyne receivers ?
...because mixer has high noise figure.
LNAs degrade overall receiver overload/jammer tolerance:
-Receiver IIP3 set by LNA IIP3 & (mixer IIP3)/(LNA gain).
-Fixed-tuned RF filter can't protect LNA & mixer
from interferers within receiver overall tuning bandwidth.
If we could make a very low noise figure mixer….
LNA would not be needed--> improved receiver IP3.
Out of band IM3 from mixer alone.
Low receiver noise (IF amp can have low Fmin).
Copyright Mark Rodwell, 2016
N-path mixers: Motivation
Why do mixers have high noise figure ?
noise partly from component noise & attenuation.
noise partly from mixer image & harmonic responses.
Can we make mixers with very low noise figure ?
good devices→ low component noise.
subsampling method→ low/zero image responses.
Copyright Mark Rodwell, 2016
Where are the harmonic responses coming from ?
sinewave. a...not
.squarewave aagainst mixing are We
elementsnonlinear signal-small
not switches, usingmix wish to weYet,
? thisdo might we How
Copyright Mark Rodwell, 2016
Array of sample-hold gates:
mixer. /not mixer,Switch
switches.h taken witSamples
cycle. signalper samples Several
form.input wave theof samples- time takesThis
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switches are There
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Copyright Mark Rodwell, 2016
Array of sample-hold gates: now sum the outputs
tiesnonlineari not switches, using are weYet,
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Copyright Mark Rodwell, 2016
Quadrature mixer with sample-hold array
mixer. quadrature
)/2sin()(sin ,)/2cos()cos(
:s weightingsine and cosineboth Provide
NnNn
Copyright Mark Rodwell, 2016
Array of sample-hold gates: harmonic tuning
selected becan harmonic desired The
Copyright Mark Rodwell, 2016
Selecting Harmonics:
trainpulseagainst
mixing :S/H One
harmonics
LOmany
NfLO /
Selecting
NfLO /2
Selecting
Copyright Mark Rodwell, 2016
N-path Filter Has No Image Responses
Array has N non-overlapping switches
unfiltered outputs: positive & negative IF images
unfiltered outputs: responses for all LO harmonics
sine/cosine weighting: selects particular LO response
sine / cosine quadrature summing suppresses IF image
Input RF filter suppresses responses beyond N*fLO.
Copyright Mark Rodwell, 2016
What is the bandwidth ?
frequency signal baseband are / and
:Assume
Nff LOsignal
0impedance Equivalent
/1 cycleduty Switch
:theorycapacitor -switched use
NZ
N
CNZ )(1/2Bandwidth 0
Copyright Mark Rodwell, 2016
N-path filter tuning
The receiver signal frequency is tuned by adjusting:
The LO (sampling) frequency (fsig = 2 fLO + fIF )
The selected LO harmonic (cos/sin weighting)
Wide tuning range is easily achieved
Copyright Mark Rodwell, 2016
N-path filter with a nonzero IF Frequency
Input gates are sample-and-filter, not sample-and-hold
No in-band resonant enhancement of voltage or current
Out-of-band voltage is suppressed at switch
→ System IM3 set by switch stage, no Q:1 degradation in dynamic range
As N → ∞ perfect conversion, image response → 0, NF →0
Copyright Mark Rodwell, 2016
With nonzero IF output frequency
phase relative 90at outputs Q and I the
summingby obtained then is mixing SSB
0
Copyright Mark Rodwell, 2016
Again, what is the bandwidth ?
frequency signal baseband are / and
:Assume
Nff LOsignal
0impedance Equivalent
/1 cycleduty Switch
:theorycapacitor -switched use
NZ
N
CNZ )(1/2Bandwidth 0
Copyright Mark Rodwell, 2016
Simulations: Late 2008, early 2009
Simulation example showing the 8 sampling phases, and the sine and cosine weighted outputs both before and
after 90 degree phase-shifting
Copyright Mark Rodwell, 2016
Simulation
CMOS switch array responses with 1st and 3rd LO harmonic tuning.
The IF bandwidth is set at 30 MHz equivalent to a Q of 100
Copyright Mark Rodwell, 2016
Simulations
File:nf-vs-N-ssampRLC
ADS Sim mark4
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1
2
3
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ise
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ure
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2 4 6 8 10 12 14 16
Number of Samplers
65nm CMOS (digital)
35nm Std InP HEMT
35nm Low Noise InP HEMT
device model: 35 nm InP/InGaAs HEMT, 400-500 GHz ft , fmaxf compared to 65nm NMOS (state of art at time of simulation)
figure. noise reduced
content harmonic LO reduced
sinewave ion toapproximatbetter
: Increased
N
Copyright Mark Rodwell, 2016
Dynamic Range
Input Capacitor C is large i.e. Z0C >> TON
Within passband, C charges to RF signal,
Current→ 0, distortion is minimized, IF amp determines IP3
Outside passband, C discharged
Current ~ Isig distortion is from current in switch element
No resonant enhancement in either case
No 3dB noise from image/harmonic response in limit as n→∞
No RF filtering needed since no LNA and mixer has high IIP3
Copyright Mark Rodwell, 2016
Simulationsdevice model: 35 nm InP/InGaAs HEMT, 400-500 GHz ft , fmaxfcompared to 65nm NMOS (state of art at time of simulation)
Copyright Mark Rodwell, 2016
65nm MOSFET Simulations – 8 element array
Simulation of in-band IM3, showing 12 dBm IIP3. Simulations showed 1.7 dB NF at 1.2 GHz12.5 dBm IIP3 is obtained with mixing against the 2nd LO harmonic (2.2 GHz inputs).
Out-of-band IM3 simulation ~0 dBm equivalent IIP3.Signals selected so that the IM3 response in-band but carriers are not.IM3 products are 20 dB stronger, so the "equivalent" IP3 has dropped 10 dB
Copyright Mark Rodwell, 2016
65nm MOSFET Simulations – 8 element array
• Simulation of in-band IM3, showing 12
dBm IIP3.
• Using the 65 nm MOS model, simulations
showed 1.7 dB NF at 1.2 GHz
• 12.5 dBm IIP3 is obtained with mixing
against the 2nd LO harmonic (2.2 GHz
inputs).
• Out-of-band IM3 simulation indicating ~0
dBm equivalent IIP3.
• Signals selected so that the IM3 response
in-band but carriers are not.
• IM3 products are 20 dB stronger, so the
"equivalent" IP3 has dropped 10 dB