ltc4211 - hot swap controller with multifunction …ltc4211 1 4211fb typical application features...

LTC4211

14211fb

TYPICAL APPLICATION

FEATURES DESCRIPTION

Hot Swap Controller with Multifunction Current Control

APPLICATIONS

L, LT, LTC, LTM, Linear Technology and the Linear logo are registered trademarks and Hot Swap is a trademark of Linear Technology Corporation. All other trademarks are the property of their respective owners.

n Allows Safe Board Insertion and Removal from a Live Backplanen Controls Supply Voltages from 2.5V to 16.5Vn Programmable Soft-Start with Inrush Current

Limiting, No External Gate Capacitor Requiredn Faster Turn-Off Time Because No External Gate

Capacitor is Requiredn Dual Level Overcurrent Fault Protectionn Programmable Response Time for Overcurrent

Protection (MS)n Programmable Overvoltage Protection (MS)n Automatic Retry or Latched Mode Operation (MS)n High Side Drive for an External N-Channel FETn User-Programmable Supply Voltage Power-Up Raten FB Pin Monitors VOUT and Signals RESETn Glitch Filter Protects Against Spurious RESET Signal

n Electronic Circuit Breakern Hot Board Insertion and Removal (Either On

Backplane or On Removable Card)n Industrial High Side Switch/Circuit Breaker

The LTC®4211 is a Hot Swap™ controller that allows a board to be safely inserted and removed from a live backplane. An internal high side switch driver controls the gate of an external N-channel MOSFET for supply voltages ranging from 2.5V to 16.5V. The LTC4211 provides soft-start and inrush current limiting during the start-up period which has a programmable duration.

Two on-chip current limit comparators provide dual level overcurrent circuit breaker protection. The slow com-parator trips at VCC – 50mV and activates in 20μs (or is programmed by an external filter capacitor, MS only). The fast comparator trips at VCC – 150mV and typically responds in 300ns.

The FB pin monitors the output supply voltage and signals the RESET output pin. The ON pin signal turns the chip on and off and can also be used for the reset function. The MS package has FAULT and FILTER pins to provide addi-tional functions like fault indication, autoretry or latch-off modes, programmable current limit response time and programmable overvoltage protection using an external Zener diode clamp.

Single Channel 5V Hot Swap Controller Power-Up Sequence

+

VCC SENSE

LTC4211

8

2

3 4

7 6

CLOAD

VOUT5V5A

GND4211 TA01A

5

1

R415k

GATE

GNDTIMER

PCB CONNECTION SENSE CTIMER10nF

FB

ONSHORT

LONGVCC5V

GNDLONG

Z1 = 1SMA10A OR SMAJ10A* OPTIONAL

RESETR210k

R120k

RX10Ω

RSENSE0.007Ω

PCB EDGECONNECTOR

(MALE) M1Si4410DY

Z1*

R336k

R510k

μPLOGIC

RESET

CX100nF

BACKPLANECONNECTOR

(FEMALE)

4211 TA01b

2.5ms/DIV

NO CLOAD

VGATE5V/DIV

VRESET5V/DIV

VON1V/DIV

VTIMER1V/DIV

LTC4211

24211fb

PIN CONFIGURATION

ABSOLUTE MAXIMUM RATINGS(Note 1)

1

2

3

4

8

7

6

5

TOP VIEW

VCC

SENSE

GATE

FB

RESET

ON

TIMER

GND

S8 PACKAGE8-LEAD PLASTIC SO

TJMAX = 125°C, θJA = 150°C/W

1

2

3

4

RESET

ON

TIMER

GND

8

7

6

5

VCCSENSE

GATE

FB

TOP VIEW

MS8 PACKAGE8-LEAD PLASTIC MSOP

TJMAX = 125°C, θJA = 200°C/W

12345

RESET

ONFILTERTIMER

GND

109876

FAULT

VCCSENSEGATEFB

TOP VIEW

MS PACKAGE10-LEAD PLASTIC MSOP

TJMAX = 125°C, θJA = 200°C/W

ORDER INFORMATION

Supply Voltage (VCC) ................................................17VInput Voltage FB, ON .................................................. –0.3V to 17V SENSE, FILTER ........................... –0.3V to VCC + 0.3V TIMER ...................................................... –0.3V to 2VOutput Voltage GATE ................................. Internally Limited (Note 3) RESET, FAULT ....................................... –0.3V to 17V

Operating Temperature Range LTC4211C ................................................ 0°C to 70°C LTC4211I ............................................. –40°C to 85°CStorage Temperature Range ..................–65°C to 150°CLead Temperature (Soldering, 10 sec) ................... 300°C

LEAD FREE FINISH TAPE AND REEL PART MARKING PACKAGE DESCRIPTION TEMPERATURE RANGE

LTC4211CS8#PBF LTC4211CS8#TRPBF 4211 8-Lead Plastic SO 0°C to 70°C

LTC4211IS8#PBF LTC4211IS8#TRPBF 4211I 8-Lead Plastic SO –40°C to 85°C

LTC4211CMS8#PBF LTC4211CMS8#TRPBF LTSC 8-Lead Plastic MSOP 0°C to 70°C

LTC4211IMS8#PBF LTC4211IMS8#TRPBF LTSD 8-Lead Plastic MSOP –40°C to 85°C

LTC4211CMS#PBF LTC4211CMS#TRPBF LTSU 10-Lead Plastic MSOP 0°C to 70°C

LTC4211IMS#PBF LTC4211IMS#TRPBF LTSV 10-Lead Plastic MSOP –40°C to 85°C

Consult LTC Marketing for parts specified with wider operating temperature ranges.

For more information on lead free part marking, go to: http://www.linear.com/leadfree/ For more information on tape and reel specifications, go to: http://www.linear.com/tapeandreel/

ELECTRICAL CHARACTERISTICS

SYMBOL PARAMETER CONDITIONS MIN TYP MAX UNITS

VCC VCC Supply Voltage Range l 2.5 16.5 V

ICC VCC Supply Current FB = High, ON = High, TIMER = Low l 1 1.5 mA

VLKO Internal VCC Undervoltage Lockout VCC Low-to-High Transition l 2.13 2.3 2.47 V

VLKOHST VCC Undervoltage Lockout Hysteresis 120 mV

IINFB FB Input Current VFB = VCC or GND ±1 ±10 μA

The l denotes the specifications which apply over the full operating temperature range, otherwise specifications are at TA = 25°C. VCC = 5V, unless otherwise noted. (Note 2)

LTC4211

34211fb

ELECTRICAL CHARACTERISTICS The l denotes the specifications which apply over the full operating temperature range, otherwise specifications are at TA = 25°C. VCC = 5V, unless otherwise noted. (Note 2)


IINON ON Input Current VON = VCC or GND ±1 ±10 μA

ILEAK RESET, FAULT Leakage Current VRESET = VFAULT = 15V, Pull-Down Device Off l ±0.1 ±2.5 μA

IINSENSE SENSE Input Current VSENSE = VCC or GND ±1 ±10 μA

VCB(FAST) SENSE Trip Voltage (VCC – VSENSE) Fast Comparator Trips l 130 150 170 mV

VCB(SLOW) SENSE Trip Voltage (VCC – VSENSE) Slow Comparator Trips l 40 50 60 mV

IGATEUP GATE Pull-Up Current Charge Pump On, VGATE ≤ 0.2V l –12.5 –10 –7.5 μA

IGATEDOWN Normal GATE Pull-Down Current ON Low l 130 200 270 μA

Fast GATE Pull-Down Current FAULT Latched and Circuit Breaker Tripped or in UVLO

50 mA

ΔVGATE External N-Channel Gate Drive VGATE – VCC (For VCC = 2.5V)VGATE – VCC (For VCC = 2.7V)VGATE – VCC (For VCC = 3.3V)VGATE – VCC (For VCC = 5V)VGATE – VCC (For VCC = 12V)VGATE – VCC (For VCC = 15V)

l

l

l

l

l

l

2.54.55.010108

8810161818

VVVVVV

VGATEOV GATE Overvoltage Lockout Threshold l 0.08 0.2 0.3 V

VFB FB Voltage Threshold FB High to Low l 1.223 1.236 1.248 V

ΔVFB FB Threshold Line Regulation 2.5V ≤ VCC ≤ 16.5V l 0.5 5 mV

VFBHST FB Voltage Threshold Hysteresis 3 mV

VONHI ON Threshold High l 1.23 1.316 1.39 V

VONLO ON Threshold Low l 1.20 1.236 1.26 V

VONHST ON Hysteresis 80 mV

IFILTER FILTER Current During Slow Fault Condition l –2.5 –2 –1.5 μA

During Normal and Reset Conditions l 7 10 13 μA

VFILTER FILTER Threshold Latched Off Threshold, FILTER Low to High l 1.20 1.236 1.26 V

VFILTERHST FILTER Threshold Hysteresis 80 mV

ITMR TIMER Current Timer On, VTIMER = 1V l –2.5 –2 –1.5 μA

Timer Off, TIMER = 1.5V 3 mA

VTMR TIMER Threshold TIMER Low to High l 1.20 1.236 1.26 V

TIMER High to Low l 0.15 0.200 0.40 V

VFAULT FAULT Threshold Latched Off Threshold, FAULT High to Low l 1.20 1.236 1.26 V

VFAULTHST FAULT Threshold Hysteresis 50 mV

VOLFAULT Output Low Voltage IFAULT = 1.6mA l 0.14 0.4 V

VOLRESET Output Low Voltage IRESET = 1.6mA l 0.14 0.4 V

tFAULTFC FAST COMP Trip to GATE Discharging VCB = 0mV to 200mV Step l 300 700 ns

tFAULTSC SLOW COMP Trip to GATE Discharging VCB = 0mV to 100mV Step, 8-Pin Version or FILTER Floating

l 10 20 30 μs

VCB = 0mV to 100mV Step,10nF at FILTER Pin to GND

l 4 6 8 ms

tEXTFAULT FAULT Low to GATE Discharging VFAULT = 5V to 0V l 1 3 5 μs

tFILTER FILTER High to FAULT Latched VFILTER = 0V to 5V l 2 4.5 7 μs

LTC4211

44211fb

TYPICAL PERFORMANCE CHARACTERISTICS


tRESET Circuit Breaker Reset Delay Time ON Low to FAULT High l 150 250 μs

tOFF Turn-Off Time ON Low to GATE Off 8 μs

ELECTRICAL CHARACTERISTICS The l denotes the specifications which apply over the full operating temperature range, otherwise specifications are at TA = 25°C. VCC = 5V, unless otherwise noted. (Note 2)

Note 1: Stresses beyond those listed under Absolute Maximum Ratings

may cause permanent damage to the device. Exposure to any Absolute

Maximum Rating condition for extended periods may affect device

reliability and lifetime.

Note 2: All current into device pins are positive; all current out of device

pins are negative; all voltages are referenced to ground unless otherwise

specified.

Note 3: An internal Zener at the GATE pin clamps the charge pump voltage

to a typical maximum operating voltage of 26V. External voltage applied to

the GATE pin beyond the internal Zener voltage may damage the part. If a

lower GATE pin voltage is desired, use an external Zener diode. The GATE

capacitance must be <0.15μF at maximum VCC.

Supply Current vs Supply Voltage Supply Current vs TemperatureUndervoltage Lockout Thresholdvs Temperature

ON Pin Threshold vs Supply Voltage

ON Pin Thresholdvs Temperature GATE Voltage vs Supply Voltage

SUPPLY VOLTAGE (V)

0

SU

PP

LY

CU

RR

EN

T (

mA

)

4.0

3.5

3.0

2.5

2.0

1.5

1.0

0.5

016

4211 G01

4 8 12 20142 6 10 18

TA = 25°C

TEMPERATURE (°C)

–75

SU

PP

LY

CU

RR

EN

T (

mA

)

2.0

2.5

3.0

125

4211 G02

1.5

1.0

0–25 25 75–50 1500 50 100

0.5

4.0

3.5

VCC = 15V

VCC = 12V

VCC = 5V

VCC = 3V

TEMPERATURE (°C)

–752.0

UN

DER

VO

LTA

GE L

OC

KO

UT T

HR

ES

HO

LD

(V

)

2.1

2.3

2.4

2.5

–25 25 50 150

4211 G03

2.2

–50 0 75 100 125

FALLING EDGE

RISING EDGE

SUPPLY VOLTAGE (V)

1.10

ON

PIN

TH

RES

HO

LD

(V

)

1.20

1.30

1.40

1.15

1.25

1.35

4 8 12 16

4211 G04

2020 6 10 14 18

TA = 25°C

HIGH THRESHOLD

LOW THRESHOLD

TEMPERATURE (°C)

–751.10

ON

PIN

TH

RES

HO

LD

(V

)

1.15

1.25

1.30

1.35

–25 25 50 150

4211 G05

1.20

–50 0 75 100 125

1.40VCC = 5V

HIGH THRESHOLD

LOW THRESHOLD

SUPPLY VOLTAGE (V)

0

GA

TE V

OLTA

GE (

V)

10

20

30

5

15

25

4 8 12 16

4211 G06

2020 6 10 14 18

TA = 25°C

LTC4211

54211fb


GATE Voltage vs Temperature VGATE – VCC vs Supply Voltage VGATE – VCC vs Temperature

GATE Output Source Currentvs Supply Voltage

Normal GATE Pull-Down Currentvs Supply Voltage

Normal GATE Pull-Down Currentvs Temperature

Fast GATE Pull-Down Currentvs Supply Voltage

GATE Output Source Currentvs Temperature

Fast GATE Pull-Down Currentvs Temperature

TEMPERATURE (°C)

–750

GA

TE V

OLTA

GE (

V)

5

15

20

25

–25 25 50 150

4211 G07

10

–50 0 75 100 125

30VCC = 15V

VCC = 12V

VCC = 5V

VCC = 3V

SUPPLY VOLTAGE (V)

00

VG

ATE –

VC

C (

V)

2

6

8

10

12 14 16 18

18

4211 G08

4

2 4 6 8 10 20

12

14

16

TA = 25°C

TEMPERATURE (°C)

–750

VG

ATE –

VC

C (

V)

2

6

8

10

75

18

4211 G09

4

0 15025–50 10050–25 125

12

14

16

VCC = 12V

VCC = 15V VCC = 5V

VCC = 3V

SUPPLY VOLTAGE (V)

7

GA

TE O

UTP

UT S

OU

RC

E C

UR

REN

T (

μA

)

9

11

13

8

10

12

4 8 12 16

4211 G10

2020 6 10 14 18

TA = 25°C

TEMPERATURE (°C)

–757

GA

TE O

UTP

UT S

OU

RC

E C

UR

REN

T (

μA

)

8

10

11

12

–25 25 50 150

4211 G11

9

–50 0 75 100 125

13

VCC = 15V

VCC = 3VVCC = 5VVCC = 12V

SUPPLY VOLTAGE (V)

140

NO

RM

AL G

ATE P

ULL-D

OW

N C

UR

REN

T (

μA

)

180

220

260

160

200

240

4 8 12 16

4211 G12

2020 6 10 14 18

TA = 25°C

TEMPERATURE (°C)

–75140

NO

RM

AL

GA

TE P

ULL-D

OW

N C

UR

REN

T (

μA

)

160

200

220

240

–25 25 50 150

4211 G13

180

–50 0 75 100 125

260VCC = 5V

SUPPLY VOLTAGE (V)

20

FAS

T G

ATE P

ULL-D

OW

N C

UR

REN

T (

mA

)

40

60

80

30

50

70

4 8 12 16

4211 G14

2020 6 10 14 18

TA = 25°C

TEMPERATURE (°C)

–7520

FAS

T G

ATE P

ULL-D

OW

N C

UR

REN

T (

mA

)

30

50

60

70

–25 25 50 150

4211 G15

40

–50 0 75 100 125

80VCC = 5V

LTC4211

64211fb


SUPPLY VOLTAGE (V)

0

FEED

BA

CK

TH

RES

HO

LD

(V

)

1.240

1.245

1.250

16

4211 G16

1.235

1.230

1.2254 8 122 186 10 14 20

TA = 25°C

HIGH THRESHOLD

LOW THRESHOLD

TEMPERATURE (°C)

–751.225

FEED

BA

CK

TH

RES

HO

LD

(V

)

1.230

1.240

1.245

1.250

–25 25 50 150

4211 G17

1.235

–50 0 75 100 125

VCC = 5V

HIGH THRESHOLD

LOW THRESHOLD

SUPPLY VOLTAGE (V)

1.10

FILTER

TH

RES

HO

LD

(V

)

1.20

1.30

1.40

1.15

1.25

1.35

4 8 12 16

4211 G18

2020 6 10 14 18

TA = 25°C

HIGH THRESHOLD

LOW THRESHOLD

TEMPERATURE (°C)

–751.10

FILTER

TH

RES

HO

LD

(V

)

1.15

1.25

1.30

1.35

–25 25 50 150

4211 G19

1.20

–50 0 75 100 125

1.40VCC = 5V

HIGH THRESHOLD

LOW THRESHOLD

SUPPLY VOLTAGE (V)

1.7

FILTER

PU

LL-U

P C

UR

REN

T (

μA

)

1.9

2.1

2.3

1.8

2.0

2.2

4 8 12 16

4211 G20

2020 6 10 14 18

TA = 25°C

TEMPERATURE (°C)

–751.7

FILTER

PU

LL-U

P C

UR

REN

T (

μA

)

1.8

2.0

2.1

2.2

–25 25 50 150

4211 G21

1.9

–50 0 75 100 125

2.3VCC = 5V

SUPPLY VOLTAGE (V)0

FILT

ER

PU

LL-D

OW

N C

UR

REN

T (

μA

)

12.0

11.5

11.0

10.5

10.0

9.5

9.0

8.5

8.016

4211 G22

4 8 12 20142 6 10 18

TA = 25°C

TEMPERATURE (°C)

–75

FILTER

PU

LL-D

OW

N C

UR

REN

T (

μA

)

10.0

10.5

11.0

125

4211 G23

9.5

9.0

8.0–25 25 75–50 1500 50 100

8.5

12.0

11.5

VCC = 5V

SUPPLY VOLTAGE (V)

1.20

TIM

ER

HIG

H T

HR

ES

HO

LD

(V

)

1.22

1.24

1.26

1.21

1.23

1.25

4 8 12 16

4211 G24

2020 6 10 14 18

TA = 25°C

Feedback Thresholdvs Supply Voltage

Feedback Thresholdvs Temperature

FILTER Threshold vs Supply Voltage

FILTER Threshold vs TemperatureFILTER Pull-Up Currentvs Temperature

FILTER Pull-Down Currentvs Supply Voltage

FILTER Pull-Down Currentvs Temperature

FILTER Pull-Up Current vs Supply Voltage

TIMER High Thresholdvs Supply Voltage

LTC4211

74211fb


TIMER High Thresholdvs Temperature

TIMER Low Thresholdvs Supply Voltage

TIMER Low Thresholdvs Temperature

TEMPERATURE (°C)

–751.20

TIM

ER

HIG

H T

HR

ES

HO

LD

(V

)

1.21

1.23

1.24

1.25

–25 25 50 150

4211 G25

1.22

–50 0 75 100 125

1.26VCC = 5V

SUPPLY VOLTAGE (V)

0

TIM

ER

LO

W T

HR

ES

HO

LD

(V

)

0.6

0.8

1.0

16

4211 G26

0.4

0.2

04 8 122 186 10 14 20

TA = 25°C

TEMPERATURE (°C)

–750

TIM

ER

LO

W T

HR

ES

HO

LD

(V

)

0.2

0.6

0.8

1.0

–25 25 50 150

4211 G27

0.4

–50 0 75 100 125

VCC = 5V

SUPPLY VOLTAGE (V)

1.70

TIM

ER

PU

LL-U

P C

UR

REN

T (

μA

)

1.90

2.10

2.30

1.80

2.00

2.20

4 8 12 16

4211 G28

2020 6 10 14 18

TA = 25°C

TEMPERATURE (°C)

–751.7

TIM

ER

PU

LL-U

P C

UR

REN

T (

μA

)

1.8

2.0

2.1

2.2

–25 25 50 150

4211 G29

1.9

–50 0 75 100 125

2.3VCC = 5V

SUPPLY VOLTAGE (V)

0

TIM

ER

PU

LL-D

OW

N C

UR

REN

T (

mA

)

2

4

6

1

3

5

4 8 12 16

4211 G30

2020 6 10 14 18

TA = 25°C

TEMPERATURE (°C)

–750

TIM

ER

PU

LL-D

OW

N C

UR

REN

T (

mA

)

1

3

4

5

–25 25 50 150

4211 G31

2

–50 0 75 100 125

6VCC = 5V

SUPPLY VOLTAGE (V)

0

VO

L (

V)

1.6

1.4

1.2

1.0

0.8

0.6

0.4

0.2

016

4211 G32

4 8 12 20142 6 10 18

TA = 25°C

RESET OR FAULT

IOL = 5mA

IOL = 1mA

TEMPERATURE (°C)

–75

VO

L (

V)

0.8

1.0

1.2

125

4211 G33

0.6

0.4

0–25 25 75–50 1500 50 100

0.2

1.6

1.4

VCC = 5V

RESET OR FAULT

IOL = 5mA

IOL = 1mA

TIMER Pull-Up Currentvs Supply Voltage

TIMER Pull-Down Currentvs Supply Voltage

TIMER Pull-Down Currentvs Temperature VOL vs Supply Voltage

TIMER Pull-Up Currentvs Temperature

VOL vs Temperature

LTC4211

84211fb


SUPPLY VOLTAGE (V)

0

VC

B (

SLO

W C

OM

P)

(mV

)

52

56

60

16

4211 G34

48

44

50

54

58

46

42

4042 86 12 14 1810 20

TA = 25°C

TEMPERATURE (°C)

–7540

VC

B (

SLO

W C

OM

P)

(mV

)

42

46

48

50

60

54

–25 25 50 150

4211 G35

44

56

58

52

–50 0 75 100 125

VCC = 5V

SUPPLY VOLTAGE (V)

0

VC

B (

FAS

T C

OM

P)

(mV

)

170

165

160

155

150

145

140

135

13016

4211 G36

4 8 12 20142 6 10 18

TA = 25°C

TEMPERATURE (°C)

–75

VC

B (

FAS

T C

OM

P)

(mV

)

150

155

160

125

4211 G37

145

140

130–25 25 75–50 1500 50 100

135

170

165

VCC = 5V

SUPPLY VOLTAGE (V)

0

SLO

W C

OM

P R

ES

PO

NS

E T

IME (

μs)

26

24

22

20

18

16

14

12

1016

4211 G38

4 8 12 20142 6 10 18

TA = 25°C8-PIN VERSIONOR FILTER FLOATING

TEMPERATURE (°C)

–75

SLO

W C

OM

P R

ES

PO

NS

E T

IME (

μs)

18

20

22

125

4211 G39

16

14

10–25 25 75–50 1500 50 100

12

26

24

8-PIN VERSION OR FILTER FLOATING

VCC = 15V

VCC = 3V

VCC = 12V

VCC = 5V

SUPPLY VOLTAGE (V)

0

FAS

T C

OM

P R

ES

PO

NS

E T

IME (

ns)

800

700

600

500

400

300

200

100

016

4211 G40

4 8 12 20142 6 10 18

TA = 25°C

VCB = 0mV TO 200mV STEP

TEMPERATURE (°C)

–75

FAS

T C

OM

P R

ES

PO

NS

E T

IME (

ns)

400

500

600

125

4211 G41

300

200

0–25 25 75–50 1500 50 100

100

800

700

VCB = 0mV TO 200mV STEP

VCC = 15V

VCC = 3VVCC = 12V

VCC = 5V

SUPPLY VOLTAGE (V)

3.0FILTER

HIG

H T

O F

AU

LT

AC

TIV

ATIO

N T

IME (

μs)

4.0

5.0

6.0

3.5

4.5

5.5

4 8 12 16

4211 G42

2020 6 10 14 18

TA = 25°C

VCB (SLOW COMP) vs Supply Voltage

VCB (SLOW COMP)vs Temperature

VCB (FAST COMP)vs Supply Voltage

VCB (FAST COMP)vs Temperature

SLOW COMP Response Time vs Temperature

FAST COMP Response Time vs Supply Voltage

SLOW COMP Response Time vs Supply Voltage

FAST COMP Response Time vs Temperature

FILTER High to FAULT Activation Time vs Supply Voltage

LTC4211

94211fb


FILTER High to FAULT Activation Time vs Temperature

Circuit Breaker RESET Timevs Supply Voltage

Circuit Breaker RESET Timevs Temperature

TEMPERATURE (°C)

–753.0FI

LTER

HIG

H T

O F

AU

LT A

CTIV

ATIO

N T

IME (

μs)

3.5

4.5

5.0

5.5

–25 25 50 150

4211 G43

4.0

–50 0 75 100 125

6.0VCC = 5V

SUPPLY VOLTAGE (V)

80

CIR

CU

IT B

REA

KER

RES

ET T

IME (

μs)

120

160

200

100

140

180

4 8 12 16

4211 G44

2020 6 10 14 18

TA = 25°C

TEMPERATURE (°C)

–7580

CIR

CU

IT B

REA

KER

RES

ET T

IME (

μs)

100

140

160

180

–25 25 50 150

4211 G45

120

–50 0 75 100 125

200VCC = 5V

SUPPLY VOLTAGE (V)

1.5

FAU

LT P

IN L

OW

TO

GA

TE D

ISC

HA

RG

ING

TIM

E (

μs)

2.5

3.5

4.5

2.0

3.0

4.0

4 8 12 16

4211 G46

2020 6 10 14 18

TA = 25°C

TEMPERATURE (°C)

–751.5

FAU

LT P

IN L

OW

TO

GA

TE D

ISC

HA

RG

ING

TIM

E (

μs)

2.0

3.0

3.5

4.0

–25 25 50 150

4211 G47

2.5

–50 0 75 100 125

4.5VCC = 5V

SUPPLY VOLTAGE (V)

0

FAU

LT T

HR

ES

HO

LD

VO

LTA

GE (

V)

1.50

1.45

1.40

1.35

1.30

1.25

1.20

1.15

1.1016

4211 G48

4 8 12 20142 6 10 18

TA = 25°C

HIGH THRESHOLD

LOW THRESHOLD

TEMPERATURE (°C)

–75

FAU

LT T

HR

ES

HO

LD

VO

LTA

GE (

V)

1.30

1.35

1.40

125

4211 G49

1.25

1.20

1.10–25 25 75–50 1500 50 100

1.15

1.50

1.45

VCC = 5V

HIGH THRESHOLD

LOW THRESHOLD

SUPPLY VOLTAGE (V)

5

TU

RN

OFF

TIM

E (

μs)

7

9

11

6

8

10

4 8 12 16

4211 G50

2020 6 10 14 18

TA = 25°C

TEMPERATURE (°C)

–755

TU

RN

OFF

TIM

E (

μs)

6

8

9

10

–25 25 50 150

4211 G51

7

–50 0 75 100 125

11VCC = 5V

FAULT Pin Low to GATE Discharging Time vs Supply Voltage

FAULT Threshold Voltage vs Supply Voltage

FAULT Threshold Voltagevs Temperature

FAULT Pin Low to GATE Discharging Time vs Temperature

Turn Off Timevs Supply Voltage Turn Off Time vs Temperature

LTC4211

104211fb


SUPPLY VOLTAGE (V)

0

GA

TE O

VER

VO

LTA

GE L

OC

KO

UT T

HR

ES

HO

LD

(V

)

0.3

0.4

0.5

16

4211 G52

0.2

0.1

04 8 122 186 10 14 20

TA = 25°C

TEMPERATURE (°C)

–750G

ATE O

VER

VO

LTA

GE L

OC

KO

UT T

HR

ES

HO

LD

(V

)

0.1

0.3

0.4

0.5

–25 25 50 150

4211 G53

0.2

–50 0 75 100 125

VCC = 5V

GATE Overvoltage Lockout Thresholdvs Supply Voltage

GATE Overvoltage Lockout Thresholdvs Temperature

PIN FUNCTIONS (8-Lead Package/10-Lead Package)

RESET (Pin 1/Pin 1): An open-drain output that pulls to GND if the voltage at the FB pin (Pin 5/Pin 6) falls below the FB pin threshold (1.236V). During the start-up cycle, the RESET pin goes high impedance at the end of the second timing cycle after the FB pin goes above the FB threshold. This pin requires an external pull-up resistor to VCC. If an undervoltage lockout condition occurs, the RESET pin pulls low independently of the FB pin to prevent false glitches.

ON (Pin 2/Pin 2): An active high signal used to enable or disable LTC4211 operation. COMP1’s high-to-low thresh-old is set at 1.236V and its hysteresis is set at 80mV. If a logic high signal is applied to the ON pin (VON > 1.316V), the first timing cycle begins if an overvoltage condition does not exist on the GATE pin (Pin 6/Pin 7). If a logic low signal is applied to the ON pin (VON < 1.236V), the GATE pin is pulled low by an internal 200μA current sink. The ON pin can also be used to reset the electronic circuit breaker. If the ON pin is cycled low and then high following a circuit breaker trip, the internal circuit breaker is reset, and the LTC4211 begins a new start-up cycle.

TIMER (Pin 3/Pin 4): A capacitor connected from this pin to GND sets the LTC4211’s system timing. The LTC4211’s initial and second start-up timing cycles and its internal “power good” delay time are defined by this capacitor.

GND (Pin 4/Pin 5): Device Ground Connection. Connect this pin to the system’s analog ground plane.

FB (Pin 5/Pin 6): The FB (Feedback) pin is an input to the COMP2 comparator and monitors the output supply voltage through an external resistor divider. If VFB < 1.236V, the RESET pin pulls low. An internal glitch filter at COMP2’s output helps prevent negative voltage transients from triggering a reset condition. If VFB > 1.239V, the RESET pin goes high at the end of the second timing cycle.

GATE (Pin 6/Pin 7): The output signal at this pin is the high side gate drive for the external N-channel FET pass transistor.

As shown in the Block Diagram, an internal charge pump supplies a 10μA gate current and sufficient gate volt-age drive to the external FET for supply voltages from 2.5V to 16.5V. The internal charge-pump and zener

LTC4211

114211fb

PIN FUNCTIONS (8-Lead Package/10-Lead Package)

clamps at the GATE pin determine the gate drive voltage (ΔVGATE = VGATE – VCC). The charge pump produces a minimum 4.5V of ΔVGATE for supplies in the range of 2.7V ≤ VCC < 4.75V. For 4.75V ≤ VCC ≤ 12V the ΔVGATE is limited by zener clamp Z1 connected between the GATE and VCC pins. The ΔVGATE is typically at 12V and with guaranteed minimum value of 10V. For VCC > 12V, the Zener clamp Z2 begins to set the limitation for ΔVGATE. Z2 clamps the gate voltage to ground to 26V typically. The minimum Z2’s clamp voltage is 23V. This effectively sets ΔVGATE to 8V minimum at VCC = 15V.

SENSE (Pin 7/Pin 8): Circuit Breaker Set Pin. With a sense resistor placed in the power path between VCC and SENSE, the LTC4211’s electronic circuit breaker trips if the voltage across the sense resistor exceeds the thresholds set inter-nally for the SLOW COMP and the FAST COMP, as shown in the Block Diagram. The threshold for the SLOW COMP is VCB(SLOW) = 50mV, and the electronic circuit breaker trips if the voltage across the sense resistor exceeds 50mV for 20μs. The SLOW COMP delay is fixed in the S8/MS8 ver-sion and adjustable in the MS version of the LTC4211. To adjust the SLOW COMP’s delay, please refer to the section on Adjusting SLOW COMP’s Response Time.

Under transient conditions where large step current changes can and do occur over shorter periods of time, a second (fast) comparator instead trips the electronic circuit breaker. The threshold for the FAST COMP is set at VCB(FAST) = 150mV, and the circuit breaker trips if the voltage across the sense resistor exceeds 150mV for more than 300ns. The FAST COMP’s delay is fixed in the LTC4211 and cannot be adjusted. To disable the electronic circuit breaker, connect the VCC and SENSE pins together.

VCC (Pin 8/Pin 9): This is the positive supply input to the LTC4211. The LTC4211 operates from 2.5V < VCC < 16.5V, and the supply current is typically 1mA. An internal undervoltage lockout circuit disables the device until the voltage at VCC exceeds 2.3V.

FAULT (Not available on S8/MS8, Pin 10 MS): FAULT is both an input and an output. Connected to this pin are an analog comparator (COMP6) and an open-drain N-channel FET. During normal operation, if COMP6 is driven below 1.236V, the electronic circuit breaker trips and the GATE pin pulls low. Typically, a 10k pull-up resistor connects to the FAULT pin. This pull-up is required to allow the LTC4211 to begin a second timing cycle (VFAULT > 1.286) and start-up properly. This also allows the use of the FAULT pin as a status output. Under normal operating conditions, the FAULT output is a logic high. Two condi-tions cause an active low on FAULT: (1) the LTC4211’s electronic circuit breaker trips because of an output short circuit causing a fast output overcurrent transient (FAST COMP trips circuit breaker); or (2) VFILTER > 1.236V. The FAULT output is driven to logic low and is latched logic low until the ON pin is driven to logic low for 150μs (the tRESET duration).

FILTER (Not available S8/MS8, Pin 3 MS): Overcurrent Fault Timing Pin and Overvoltage Fault Set pin. With a capacitor connected from this pin to ground, the SLOW COMP’s response time can be adjusted. In the S8/MS8 version of the LTC4211, the FILTER pin is not available and the delay time from overcurrent detect to GATE OFF is fixed at 20μs.

LTC4211

124211fb

BLOCK DIAGRAM

–

+

VREF VREF

–+

+–

+–

SLOWCOMP

50mV 150mV

0.2V

COMP7

M3

GLITCH FILTER(SEE NOTE 1)

UVLO

–+FASTCOMP

– + – +

300nsDELAY

GLITCH FILTER150μs

GLITCH FILTERFUNCTION OFOVERDRIVE

BG

VREF

0.2V

VREF = 1.236V

CBTRIPSOR UVLO ON LOW

START-UPCURRENT

REGULATORGATE

CHARGING

200μA 10μA

POWER BAD

CB TRIPS

VREF

10μA

6 (7)GATE7 (8)SENSE8 (9)VCC

M1

CHARGEPUMP

Z1VZ (TYP) = 12V

M2

GND

4 (5)

FAULT

(10)MS ONLY

–

+

COMP1

2 ON 5 (6) 4211 BDFB

COMP2

–

+

–

+

COMP3

tTIMER

0.2V

VREF

COMP4

–

+

VREF

COMP5

NORMAL, RESET

NOTE 1: SET BY FILTER CAPACITOR FOR MS 20μs DEFAULT FOR MS8, S8

PIN NUMBERS FOR S8/MS8 (MS)

NORMAL

FAULT

TIMER

3 (4)

FILTER

(3) MS ONLY

2μA

M6

M5

VCC

2μA

M4

VCC

10μA

LOGIC

RESET

1

COMP6

Z2VZ (TYP) = 26V

VCC

LTC4211

134211fb

OPERATION

+

SENSE

RSENSE

R2

R1R310k

7

VCC

VOUT

8

GATELTC4211

6

2

FB

Q2

GND

ON

4211 F01

1RESET

5

CTIMER

3

TIMER

4

CLOAD

Q1

LOGIC

TIMER1.236V

REFERENCE

COMP2

μP

RESET

SHORT

LONGVCC

ON/RESET

GNDLONG

PCB EDGECONNECTOR

(MALE)

BACKPLANECONNECTOR

(FEMALE)

+

–

VOUT

TIMER

RESET

V2 V2V1V1

1.236V

POWER GOODDELAY

1 2 3 4

4211 F02

Figure 1. Supply Voltage Monitor Block Diagram

Figure 2. Supply Monitor Waveforms in Normal Mode

HOT CIRCUIT INSERTION

When circuit boards are inserted into or removed from live backplanes, the supply bypass capacitors can draw huge transient currents from the backplane power bus as they charge. The transient current can cause permanent damage to the connector pins as well as cause glitches on the system supply, causing other boards in the system to reset.

The LTC4211 is designed to turn a printed circuit board’s supply voltages ON and OFF in a controlled manner, al-lowing the circuit board to be safely inserted or removed from a live backplane. The device provides a system reset signal to indicate when board supply voltage drops below a predetermined level, as well as a dual function fault monitor.

OUTPUT VOLTAGE MONITOR

The LTC4211 uses a 1.236V bandgap reference, precision voltage comparator and an external resistor divider to monitor the output supply voltage as shown in Figure 1.

The operation of the supply monitor in normal mode is illustrated in Figure 2. When the voltage at the FB pin drops below its reset threshold (1.236V), the comparator

COMP2 output goes high. After a glitch filter delay, RESET is pulled low (Time Point 1). When the voltage at the FB pin rises above its reset threshold (1.239V), COMP2’s output goes low and a timing cycle starts (Time Point 4). After a complete timing cycle, RESET is pulled high by the external pull-up resistor. If the FB pin rises above the reset threshold for less than a timing cycle, the RESET output remains low (Time Points 2 to 3).

As shown in Figure 5, the LTC4211’s RESET pin is logic low during any undervoltage lockout condition and during the initial insertion of a PC board. Under normal opera-tion, RESET goes to logic high at the end of the soft-start cycle only after the FB pin voltage rises above its reset threshold of 1.239V.

LTC4211

144211fb

OPERATIONUNDERVOLTAGE LOCKOUT

The LTC4211’s power-on reset circuit initializes the start-up procedure and ensures the chip is in the proper state if the input supply voltage is too low. If the supply voltage falls below 2.18V, the LTC4211 is in undervoltage lockout (UVLO) mode, and the GATE pin is pulled low. Since the UVLO circuitry uses hysteresis, the chip restarts after the supply voltage rises above 2.3V and the ON pin goes high.

In addition, users can utilize the ON comparator (COMP1) or the FAULT comparator (COMP6) to effectively program a higher undervoltage lockout level. Figure 3 shows how the external resistor divider at the ON pin programs the system’s undervoltage lockout voltage. The system will enter the plug-in cycle after the ON pin rises above 1.316V. The resistor divider sets the circuit to turn on when VCC reaches around 79% of its final value. If a different turn on VCC voltage is desired change the resistor divider values accordingly. Alternatively, the FAULT comparator can be used to configure the external undervoltage lockout level. If the FAULT comparator is used for this purpose, the system will wait for the input voltage to increase above the level set by the user before starting the second timing cycle. Also, if the input voltage drops below the set level in normal operating mode, the user must cycle the ON pin or VCC to restart the system.

GLITCH FILTER FOR RESET

The LTC4211 has a glitch filter to prevent transients on the FB pin from generating a system reset. The relationship between glitch filter time and the FB transient voltage is shown in Figure 4.

Figure 4. FB Comparator Glitch Filter Time vs Feedback Transient Voltage

Figure 3. ON Pin Sets the Undervoltage Lockout Voltage Externally

SYSTEM TIMING

System timing for the LTC4211 is generated at the TIMER pin (see the Block Diagram). If the LTC4211’s internal timing circuit is off, an internal N-channel FET connects the TIMER pin to GND. If the timing circuit is enabled, an internal 2μA current source is then connected to the TIMER pin to charge CTIMER at a rate given by Equation 1:

CTIMER Charge-Up Rate = 2µA

CTIMER

(1)

When the TIMER pin voltage reaches COMP4’s threshold of 1.236V, the TIMER pin is reset to GND. Equation 2 gives an expression for the timer period:

tTIMER = 1.236V •CTIMER

2µA

(2)

As a design aid, the LTC4211’s timer period as a function of the CTIMER using standard values from 3.3nF to 0.33μF is shown in Table 1.

VIN3.3V

R110k

R210k

ON PIN

(a) 3.3VIN

VIN5V

R120k

R210k

ON PIN

(b) 5VIN

VIN12V

R161.9k

R210k

ON PIN

(c) 12VIN

4211 F03

FB TRANSIENT (mV)

0

GLIT

CH

FIL

TER

TIM

E (

μs)

150

200

250

160

4211 F04

100

50

040 80 12020 18060 100 140 200

TA = 25°C

LTC4211

154211fb

OPERATIONThe CTIMER value is vital to ensure a proper start-up and reliable operation. A system may not start up if a timing period is set too short relative to the time needed for the output voltage to ramp up from zero to its rated value. Conversely, this timing period should not be too long as an output short can occur at start-up causing the exter-nal MOSFET to overheat. A good starting point is to set CTIMER = 10nF and adjust its value accordingly to suit the specific applications.

OPERATING SEQUENCE

Power-Up, Start-Up Check and Plug-In Timing Cycle

The sequence of operation for the LTC4211 is illustrated in the timing diagram of Figure 5. When a PC board is inserted into a live backplane, the LTC4211 first performs

Figure 5. Normal Power-Up Sequence

VCC

ON

2μA 2μA

10μA

PLUG-IN CYCLEFIRST TIMING CYCLE

200μA

POWERGOOD(VFB > VREF)

VTMR = VREF

TIMER

1 2 3 4 5 6 7 8 9

RESET PULLED LOW DUE TO POWER BAD

10

SLOW COMPARATOR ARMEDCHECK FOR GATE < 0.2VFAST COMPARATOR ARMED

CHECK FOR FILTER LOW (<VREF – 80mV)CHECK FOR FAULT HIGH (>VREF + 50mV)

ON GOES LOW

GATE

VOUT

RESET

POWER BAD(VFB < VREF)

SOFT-START CYCLESECOND TIMING CYCLE

4211 F05

Table 1. tTIMER vs CTIMER

CTIMER tTIMER

0.0033μF 2.0ms

0.0047μF 2.9ms

0.0068μF 4.2ms

0.0082μF 5.1ms

0.01μF 6.2ms

0.015μF 9.3ms

0.022μF 13.6ms

0.033μF 20.4ms

0.047μF 29.0ms

0.068μF 42.0ms

0.082μF 50.7ms

0.1μF 61.8ms

0.15μF 92.7ms

0.22μF 136ms

0.33μF 204ms

LTC4211

164211fb

OPERATIONa start-up check to make sure the supply voltage is above its 2.3V UVLO threshold (see Time Point 1). If the input supply voltage is valid, the gate of the external pass tran-sistor is pulled to ground by the internal 200μA current source connected at the GATE pin. The TIMER pin is held low by an internal N-channel pull-down transistor (see M6, LTC4211 Block Diagram) and the FILTER pin voltage is pulled to ground by an internal 10μA current source.

Once VCC and ON (the ON pin is >1.316) are valid, the LTC4211 checks to make sure that GATE is OFF (VGATE < 0.2V) at Time Point 2. An internal timing circuit is enabled and the TIMER pin voltage ramps up at the rate described by Equation 1. At Time Point 3 (the timing period programmed by CTIMER), the TIMER pin voltage equals VTMR (1.236V). Next, the TIMER pin voltage ramps down to Time Point 4 where the LTC4211 performs two checks: (1) FILTER pin voltage is low (VFILTER < 1.156V) and (2) FAULT pin volt-age is high (VFAULT > 1.286V). If both conditions are met, the LTC4211 begins a second timing (soft-start) cycle.

Second Timing (Soft-Start) Cycle

At the beginning of the second timing cycle (Time Point 5), the LTC4211’s FAST COMP is armed and an internal 10μA current source working with an internal charge pump provides the gate drive to the external pass transistor. The LTC4211 automatically limits the inrush current in one of two ways: by controlling the GATE pin voltage slew rate or by actively limiting the inrush current. If GATE voltage slew rate control is preferred, an external capacitor CGATE can be used from GATE to ground, as shown in Figure 6.

An expression for the GATE voltage slew rate is given by Equation 3:

VGATE Slew Rate,

dVGATEdt

= 10µACGATE

(3)

Adding CGATE slows the GATE voltage slew rate at the ex-pense of slower system turn-on and turn-off time. Should this technique be used, values for CGATE less than 150nF are recommended.

The inrush current being delivered to the load while the GATE is ramping is dependent on CLOAD and CGATE. Equation 4 gives an expression for the inrush current during the second timing cycle:

IINRUSH =dVGATE

dt• CLOAD = 10µA •

CLOADCGATE

(4)

For example, if CGATE = 3300pF and CLOAD = 2000μF, the inrush current charging CLOAD is:

IINRUSH = 10µA •

2000µF0.0033µF

= 6.06A

(5)

At Time Point 6, the output voltage trips COMP2’s thresh-old, signaling an output voltage “power good” condition. At Time Point 7, RESET is asserted high, SLOW COMP is armed and the LTC4211 enters a fault monitor mode. The TIMER voltage then ramps down to Time Point 8.

Power-Off Cycle

As shown at Time Point 9, an external hard reset is initiated by pulling the ON pin low (VON < 1.236V). The GATE pin voltage is ramped to ground by the internal 200μA cur-rent source, discharging CGATE and turning off the pass transistor. As CLOAD discharges, the output voltage crosses COMP2’s threshold, signaling a “power bad” condition at Time Point 10. At this point, RESET is asserted low.

Figure 6. Using an External Capacitor at GATE for GATE Voltage Slew Rate Control

M1Si4410DY

RSENSE0.007Ω

CGATE*

CLOAD

4211 F06

+

VCC SENSE

LTC4211**

GATE

FB

R136k

VOUT5V5A

VIN5V

R215k

***

VALUES ≤150nF SUGGESTEDADDITIONAL DETAILS OMITTED FOR CLARITY =

dVGATE

dt

VGATE SLEW RATE CONTROL

10μA

CGATE( )

LTC4211

174211fb

OPERATIONSOFT-START WITH CURRENT LIMITING

During the second timing cycle, the inrush current was described by Equation 4. Note that there is a one-to-one correspondence in the inrush current to CLOAD. If the inrush current is large enough to cause a voltage drop greater than 50mV across the sense resistor, an internal servo loop controls the operation of the 10μA current source at the GATE pin to regulate the load current to:

ILIMIT(SOFTSTART) = 50mV

RSENSE

(6)

For example, the inrush current is limited to 5A when RSENSE = 0.01Ω.

In this fashion, the inrush current is controlled and CLOAD is charged up slowly during the soft-start cycle.

The timing diagram in Figure 7 illustrates the operation of the LTC4211 in a normal power-up sequence with lim-ited inrush current as described by Equation 6. At Time Point 5, the GATE pin voltage begins to ramp and the power MOSFET starts to charge CLOAD. At Time Point 5A, the inrush current causes a 50mV voltage drop across RSENSE and the internal servo loop engages, limiting the inrush cur-rent to a fixed level. At Time Point 6, the GATE pin voltage continues to ramp as CLOAD charges until VOUT reaches its final value. The charging current reduces, and the internal servo loop disengages. At the end of the soft-start cycle (Time Point 7), RESET is high and SLOW COMP is armed.

Figure 7. Normal Power-Up Sequence (with Current Limiting in Second Timing Cycle)

PLUG-IN CYCLEFIRST TIMING CYCLE

TIMER

ON

VCC

1 2 3 4 5 6 7 8 9

RESET PULLED LOW DUE TO POWER BAD

10

200μA

4211 F07

2μA2μA

VREF

10μA

GATE

VOUT

POWER BADVFB < VREF

5A

SLOW COMPARATOR ARMEDCHECK FOR GATE < 0.2VFAST COMPARATOR ARMED

CHECK FOR FILTER LOW (<VREF – 80mV)CHECK FOR FAULT HIGH (>VREF + 50mV)

ON GOES LOW

GATE

VOUT

ILOAD

RESET

SOFT-START CYCLESECOND TIMING CYCLE

POWER GOODVFB > VREF

LOAD CURRENT IS REGULATING AT 50mV/RSENSE

LTC4211

184211fb

OPERATIONbreaker if the voltage across the SENSE resistor (VCC – VSENSE = VCB) is greater than 50mV for 20μs. There may be applications where this comparator’s response time is not long enough, for example, because of excessive supply voltage noise. To adjust the response time of the SLOW COMP, the MS version of the LTC4211 is chosen and a capacitor is used at the LTC4211’s FILTER pin (see section on Adjusting SLOW Comp’s Response Time). The FAST COMP trips the circuit breaker to protect against fast load overcurrents if the transient voltage across the sense resistor is greater than 150mV for 300ns. The response time of the LTC4211’s FAST COMP is fixed.

The timing diagram of Figure 7 illustrates when the LTC4211’s electronic circuit breaker is armed. After the first timing cycle, the LTC4211’s FAST COMP is armed at Time Point 5. Arming FAST COMP at Time Point 5 en-sures that the system is protected against a short-circuit condition during the second timing cycle. At Time Point 7, SLOW COMP is armed when the internal control loop is disengaged.

The timing diagrams in Figures 8 and 9 illustrate the op-eration of the LTC4211 when the load current conditions exceed the thresholds of the FAST COMP (VCB(FAST) > 150mV) and SLOW COMP (VCB(SLOW) > 50mV), respec-tively.

RESETTING THE ELECTRONIC CIRCUIT BREAKER

Once the LTC4211’s circuit breaker is tripped, FAULT is asserted low and the GATE pin is pulled to ground. The LTC4211 remains latched OFF in this fault state until the external fault is cleared. To clear the internal fault detect circuitry and to restart the LTC4211, its ON pin must be driven low (VON < 1.236V) for at least 150μs, after which time FAULT goes high. Toggling the ON pin from low to high (VON > 1.316V) initiates a restart sequence in the LTC4211. The timing diagram in Figure 10 illustrates a start-up sequence where the LTC4211 is powered up into a load overcurrent condition. Note that the circuit breaker trips at Time Point B and is reset at Time Point 9A.

FREQUENCY COMPENSATION AT SOFT-START

If the external gate capacitance is greater than 600pF, no external gate capacitor is required at GATE to stabilize the internal current-limiting loop during soft-start. Oth-erwise, connect a gate capacitor between the GATE pin and ground to increase the total gate capacitance to be equal to or above 600pF. The servo loop that controls the external MOSFET during current limiting has a unity-gain frequency of about 105kHz and phase margin of 80° for external MOSFET gate input capacitances to 2.5nF.

USING AN EXTERNAL GATE CAPACITOR

In addition to reducing the inrush current (Equation 4), an external gate capacitor (Figure 6) may also be useful to decrease or eliminate current spikes through the MOSFET when power is first applied. At power-up, the instantaneous input voltage step attempts to pull the MOSFET gate up through the MOSFET’s drain-to-gate capacitance. If the MOSFET’s CGS is small, the gate can be pulled up high enough to turn on the MOSFET, thereby allowing a cur-rent spike to the output. This event occurs during the time that the LTC4211 is coming out of UVLO and getting its intelligence to hold the GATE pin low. An external capaci-tor attenuates the voltage to which the GATE is pulled up and eliminates the current spike. The value required is dependent on the MOSFET capacitance specifications. In typical applications, this capacitor is not required.

ELECTRONIC CIRCUIT BREAKER

The LTC4211 features an electronic circuit breaker function that protects against externally-generated fault conditions and shorts or excessive load current and can also be con-figured to protect against input supply overvoltage. If the circuit breaker trips, the GATE pin is immediately pulled to ground, the external N-channel MOSFET is quickly turned OFF and FAULT is latched low.

The circuit breaker trips whenever the voltage across the sense resistor exceeds two different levels, set by the LTC4211’s SLOW COMP and FAST COMP thresholds (see Block Diagram). The SLOW COMP trips the circuit

LTC4211

194211fb

OPERATION

GATE

TIMER

VCC ON

1 2 3 4 5 6 7 8

GATE

VOUT

A

SHORT CIRCUIT RESET PULLED LOW DUE TO POWER BAD

B C

SLOW COMPARATOR ARMED

CIRCUIT BREAKER TRIPS

FAST COMPARATOR ARMED

VOUT

VCC – VSENSE

FAULT

RESET


POWER BADVFB < VREF

FPD

>150mV

4211 F08300ns

TYP

Figure 8. Output Short Circuit Causes Fast Comparator to Trip the Circuit Breaker

LTC4211

204211fb

OPERATION

GATE

TIMER

VCC

1 2 3 4 5 6 7 8 A

OVER CURRENT RESET PULLED LOW DUE TO POWER BAD

B C




10μA2μA

VREF

POWER BADVFB < VREF

FPD

GATE

VOUT

>50mV

4211 F09


VOUT

VCC – VSENSE

FILTER

FAULT

RESET

ON


Figure 9. Mild Overcurrent Slow Comparator Trips the Circuit Breaker After Filter Programming Period

LTC4211

214211fb

OPERATION

GATE

TIMER

VCC

1 2 3 4 5 6

GATE

VFB < VREF

>50mV

VREF

10μA

4211 F10

tRESET

tFAULTSC

2μA

FPD

VOUT

7 8 B 9 9A 1



CIRCUIT BREAKER RESET


VOUT

VCC – VSENSE

FILTER

FAULT

RESET

ON ONON

VSENSE = 50mV

REGULATINGLOAD CURRENT

Figure 10. Power-Up in Overcurrent, Slow Comparator Trips the Circuit Breaker

ADJUSTING SLOW COMP’S RESPONSE TIME

The response time of SLOW COMP is adjusted using a capacitor connected from the LTC4211’s FILTER pin to ground. If this pin is left unused, SLOW COMP’s delay defaults to 20μs. During normal operation, the FILTER output pin is held low as an internal 10μA pull-down current source is connected to this pin by transistor M4. This pull-down current source is turned off when an overcurrent load condition is detected by SLOW COMP. During an overcurrent condition, the internal 2μA pull-up current source is connected to the FILTER pin by transistor M5, thereby charging CFILTER. As the charge on the capacitor accumulates, the voltage across CFILTER increases. Once the FILTER pin voltage increases to 1.236V, the electronic circuit breaker trips and the LTC4211’s

GATE pin is switched quickly to ground by transistor M3. After the circuit breaker is tripped, M5 is turned OFF, M4 is turned ON and the 10μA pull-down current then holds the FILTER pin voltage low.

The SLOW COMP response time from an overcurrent fault condition to when the circuit breaker trips (GATE OFF) is given by Equation 7:

tSLOWCOMP = 1.236V •

CFILTER2µA

+ 20µs

(7)

For example, if CFILTER = 1000pF, SLOW COMP’s response time = 638μs. As a design aid, SLOW COMP’s delay time (tSLOW COMP) versus CFILTER for standard values of CFILTER from 100pF to 1000pF is illustrated in Table 2.

LTC4211

224211fb

OPERATION

SENSE RESISTOR CONSIDERATIONS

The fault current level at which the LTC4211’s internal electronic circuit breaker trips is determined by a sense resistor connected between the LTC4211’s VCC and SENSE pins and two separate trip points. The first trip point is set by the SLOW COMP’s threshold, VCB(SLOW) = 50mV, and occurs should a load current fault condition exist for more than 20μs. The current level at which the electronic circuit breaker trips is given by Equation 8:

ITRIP(SLOW) =

VCB(SLOW)

RSENSE= 50mV

RSENSE

(8)

The second trip point is set by the FAST COMP’s threshold, VCB(FAST) = 150mV, and occurs during fast load current transients that exist for 300ns or longer. The current level at which the circuit breaker trips in this case is given by Equation 9:

ITRIP(FAST) =VCB(FAST)

RSENSE= 150mV

RSENSE

(9)

As a design aid, the currents at which the electronic circuit breaker trips for common values for RSENSE are shown in Table 3.

Figure 11. Making PCB Connections to the Sense Resistor

Table 2. tSLOWCOMP vs CFILTER

CFILTER tSLOWCOMP

100pF 82μs

220pF 156μs

330pF 224μs

470pF 310μs

680pF 440μs

820pF 527μs

1000pF 638μs

Table 3. ITRIP(SLOW) and ITRIP(FAST) vs RSENSE

RSENSE ITRIP(SLOW) ITRIP(FAST)

0.005Ω 10A 30A

0.006Ω 8.3A 25A

0.007Ω 7.1A 21A

0.008Ω 6.3A 19A

0.009Ω 5.6A 17A

0.01Ω 5A 15A

For proper circuit breaker operation, Kelvin-sense PCB connections between the sense resistor and the LTC4211’s VCC and SENSE pins are strongly recommended. The drawing in Figure 11 illustrates the correct way of making connections between the LTC4211 and the sense resis-tor. PCB layout should be balanced and symmetrical to minimize wiring errors. In addition, the PCB layout for the sense resistor should include good thermal management techniques for optimal sense resistor power dissipation.

The power rating of the sense resistor should accommodate steady-state fault current levels so that the component is not damaged before the circuit breaker trips. Table 4 in the Appendix lists sense resistors that can be used with the LTC4211’s circuit breaker.

IRC-TT SENSE RESISTORLR251201R010FOR EQUIVALENT

0.01, 1%, 1W

CURRENT FLOWTO LOAD

CURRENT FLOWTO LOAD

TOVCC

TOSENSE

TRACK WIDTH W:0.03" PER AMP

ON 1 OZ COPPERW

4211 F11

CALCULATING CIRCUIT BREAKER TRIP CURRENT

For a selected RSENSE value, the nominal load current that trips the circuit breaker is given by Equation 10:

ITRIP(NOM) =VCB(NOM)

RSENSE(NOM)= 50mV

RSENSE(NOM)

(10)

The minimum load current that trips the circuit breaker is given by Equation 11.

ITRIP(MIN) =VCB(MIN)

RSENSE(MAX)= 40mV

RSENSE(MAX)

(11)

where

RSENSE(MAX) = RSENSE(NOM) 1+

RTOL100

⎛

⎝⎜

⎞

⎠⎟

⎡

⎣

⎢⎢

⎤

⎦

⎥⎥

LTC4211

234211fb

OPERATIONThe maximum load current that trips the circuit breaker is given in Equation 12.

ITRIP(MAX) =VCB(MAX)

RSENSE(MIN)= 60mV

RSENSE(MIN)

(12)

where

RSENSE(MIN) =RSENSE(NOM) 1–

RTOL100

⎛

⎝⎜

⎞

⎠⎟

⎡

⎣

⎢⎢

⎤

⎦⎥⎥

For example:

If a sense resistor with 7mΩ ±5% RTOL is used for current limiting, the nominal trip current ITRIP(NOM) = 7.1A. From Equations 11 and 12, ITRIP(MIN) = 5.4A and ITRIP(MAX) = 9.02A respectively.

For proper operation and to avoid the circuit breaker trip-ping unnecessarily, the minimum trip current (ITRIP(MIN)) must exceed the circuit’s maximum operating load current. For reliability purposes, the operation at the maximum trip current (ITRIP(MAX)) must be evaluated carefully. If necessary, two resistors with the same RTOL can be con-nected in parallel to yield an RSENSE(NOM) value that fits the circuit requirements.

POWER MOSFET SELECTION CRITERIA

To start the power MOSFET selection process, choose the maximum drain-to-source voltage, VDS(MAX), and the maxi-mum drain current, ID(MAX) of the MOSFET. The VDS(MAX) rating must exceed the maximum input supply voltage (including surges, spikes, ringing, etc.) and the ID(MAX) rating must exceed the maximum short-circuit current in the system during a fault condition. In addition, consider three other key parameters: 1) the required gate-source (VGS) voltage drive, 2) the voltage drop across the drain-to-source on resistance, RDS(ON) and 3) the maximum junction temperature rating of the MOSFET.

Power MOSFETs are classified into three categories: standard MOSFETs (RDS(ON) specified at VGS = 10V) logic-level MOSFETs (RDS(ON) specified at VGS = 5V), and sub-logic-level MOSFETs (RDS(ON) specified at VGS = 2.5V). The absolute maximum rating for VGS is typically ±20V for

standard MOSFETs. However, the VGS maximum rating for logic-level MOSFETs ranges from ±8V to ±20V depend-ing upon the manufacturer and the specific part number. The LTC4211’s GATE overdrive as a function of VCC is illustrated in the Typical Performance curves. Logic-level and sub-logic-level MOSFETs are recommended for low supply voltage applications and standard MOSFETs can be used for applications where supply voltage is greater than 4.75V.

Note that in some applications, the gate of the external MOSFET can discharge faster than the output voltage when the circuit breaker is tripped. This causes a nega-tive VGS voltage on the external MOSFET. Usually, the selected external MOSFET should have a ±VGS(MAX) rat-ing that is higher than the operating input supply voltage to ensure that the external MOSFET is not destroyed by a negative VGS voltage. In addition, the ±VGS(MAX) rating of the MOSFET must be higher than the gate overdrive voltage. Lower ±VGS(MAX) rating MOSFETs can be used with the LTC4211 if the GATE overdrive is clamped to a lower voltage. The circuit in Figure 12 illustrates the use of Zener diodes to clamp the LTC4211’s GATE overdrive signal if lower voltage MOSFETs are used.

Figure 12. Optional Gate Clamp for Lower VGS(MAX) MOSFETs

VCC VOUT

*USER SELECTED VOLTAGE CLAMP(A LOW BIAS CURRENT ZENER DIODE IS RECOMMENDED)1N4688 (5V)1N4692 (7V): LOGIC-LEVEL MOSFET1N4695 (9V)1N4702 (15V): STANDARD-LEVEL MOSFET

4211 F12

RSENSE

GATE

D2*D1*

Q1

RG200Ω

The RDS(ON) of the external pass transistor should be low to make its drain-source voltage (VDS) a small percentage of VCC. At a VCC = 2.5V, VDS + VRSENSE = 0.1V yields 4% error at the output voltage. This restricts the choice of MOSFETs to very low RDS(ON). At higher VCC voltages, the VDS requirement can be relaxed in which case MOSFET package dissipation (PD and TJ) may limit the value of

LTC4211

244211fb

OPERATIONRDS(ON). Table 5 lists some power MOSFETs that can be used with the LTC4211.

For reliable circuit operation, the maximum junction temperature (TJ(MAX)) for a power MOSFET should not exceed the manufacturer’s recommended value. This includes normal mode operation, start-up, current-limit and autoretry mode in a fault condition. Under normal conditions the junction temperature of a power MOSFET is given by Equation 13:

MOSFET Junction Temperature, TJ(MAX) ≤ TA(MAX) + θJA • PD (13)

where

PD = (ILOAD)2 • RDS(ON)

θJA = junction-to-ambient thermal resistance

TA(MAX) = maximum ambient temperature

If a short circuit happens during start-up, the external MOSFET can experience a big single pulse energy. This is especially true if the applications only employ a small gate capacitor or no gate capacitor at all. Consult the safe operating area (SOA) curve of the selected MOSFET to ensure that the TJ(MAX) is not exceeded during start-up.

USING STAGGERED PIN CONNECTORS

The LTC4211 can be used on either a printed circuit board or on the backplane side of the connector, and examples for both are shown in Figures 13 and 14. Printed circuit board edge connectors with staggered pins are recom-mended as the insertion and removal of circuit boards do sequence the pin connections. Supply voltage and ground connections on the printed circuit board should be wired to the edge connector’s long pins or blades. Control and status signals (like RESET, FAULT and ON) passing through the card’s edge connector should be wired to short length pins or blades.

PCB CONNECTION SENSE

There are a number of ways to use the LTC4211’s ON pin to detect whether the printed circuit board has been fully seated in the backplane before the LTC4211 commences a start-up cycle.

The first example is shown in the schematic on the front page of this data sheet. In this case, the LTC4211 is mounted on the PCB and a 20k/10k resistive divider is connected to the ON pin. On the edge connector, R1 is wired to a short pin. Until the connectors are fully mated, the ON pin is held low, keeping the LTC4211 in an OFF state. Once the connectors are mated, the resistive divider is connected to VCC, VON > 1.316V and the LTC4211 begins a start-up cycle.

In Figure 13, an LTC4211 is illustrated in a basic configura-tion on a PCB daughter card. The ON pin is connected to VCC on the backplane through a 10k pull-up resistor once the card is seated into the backplane. R2 bleeds off any potential static charge which might exist on the backplane, the connector or during card installation.

A third example is shown in Figure 14 where the LTC4211 is mounted on the backplane. In this example, a 2N2222 transistor and a pair of resistors (R4, R5) form the PCB connection sense circuit. With the card out of the chassis, Q2’s base is biased to VCC through R5, biasing Q2 ON and driving the LTC4211’s ON pin low. The base of Q2 is also wired to a socket on the backplane connector. When a card is firmly seated into the backplane, the base of Q2 is then grounded through a short pin connection on the card. Q2 is biased OFF, the LTC4211’s ON pin is pulled-up to VCC and a start-up cycle begins.

In the previous three examples, the connection sense was hard wired with no processor (low) interrupt capability. As illustrated in Figure 15, the addition of an inexpensive logic-level discrete MOSFET and a couple of resistors offers processor interrupt control to the connection sense. R4 keeps the gate of M2 at VCC until the card is firmly mated to the backplane. A logic low for the ON/OFF signal turns M2 OFF, allows the ON pin to pull high and turns on the LTC4211.

LTC4211

254211fb

APPLICATIONS INFORMATION

A more elaborate connection sense scheme is shown in Figure 16. The bases of Q1 and Q2 are wired to short pins located on opposite ends of the edge connector because the installation/removal of printed circuit cards gener-ally requires rocking the card back and forth. When VCC makes connection, the bases of transistors Q1 and Q2 are pulled high, biasing them ON. When either one of them is ON, the LTC4211’s ON pin is held low, keeping the LTC4211 OFF. When both the short base connector

+VCCRESET

SENSEON

R515k

LTC4211

GATE

FB

8

7

6

5

4211 F13

1

2

4

3CTIMER10nF

GND

TIMER

R436k

VOUT5V5A

Q1Si4410DY

RSENSE0.007Ω

COUT

R610k

Z1*


R110Ω

C10.1μF

R210k

VIN5V

SHORT

LONG5VVCC

RESET

LONG

PCB EDGECONNECTOR

(MALE)

SHORT

BACKPLANECONNECTOR

(FEMALE)

+

VCC SENSE

ON

R2100k

RESET

LTC4211

GATE

FB

78

6

1

5


4211 F14

2

4

3CTIMER10nF

R310k

GND

TIMER

RESET

VOUT5V5A

Q1Si4410DY

RSENSE0.007Ω

COUT

R136k

R410k

R510k

PCBCONNECTION

SENSE

RX10Ω

CX0.1μF

Z1*

VIN5V

SHORT

LONG

SHORT

PCB EDGECONNECTOR

(MALE)

LONG

SHORT

BACKPLANECONNECTOR

(FEMALE)

Q2

R715k

pins of Q1 and Q2 finally mate to the backplane, their bases are grounded, biasing the transistors OFF. The ON pin voltage is then pulled high by R3 enabling the LTC4211 and a power-up cycle begins.

A software-initiated power-down cycle can be started by momentarily driving transistor M1 with a logic high signal. This in turn will drive the LTC4211’s ON pin low. If the ON pin is held low for more than 8μs, the LTC4211’s GATE pin is switched to ground.

Figure 13. Hot Swap Controller On Daughter Board (Staggered Pin Connections)

Figure 14. Hot Swap Controller on Backplane (Staggered Pin Connections)

LTC4211

264211fb


+

VCC SENSE

LTC4211

8

2

3 4

7 6

CLOAD

VOUT5V5A

4211 F15

5

1

R615k

GATE

GNDTIMER


CTIMER10nF

FB

ONSHORT

LONGVCC5V

GND

ON/OFF

LONG

ZZ1 = 1SMA10A OR SMAJ10AM2: 2N7002LT1* OPTIONAL

RESETR210k

R410k

M2

R110k

RX10Ω

RSENSE0.007Ω

PCB EDGECONNECTOR

(MALE) M1Si4410DY

Z1*

R536k

R710k

μPLOGIC

RESETSHORT

CX100nF

BACKPLANECONNECTOR

(FEMALE)

+

VCC SENSE

LTC4211

8

2

3 4

7 6

CLOAD

VOUT5V5A

4211 F16

5

1

R515k

GATE

GNDTIMER


CTIMER10nF

FB

ON

LONGVCC

GND

ON/RESET

LONG

RESET

M1

RX10Ω

RSENSE0.007Ω

PCB EDGECONNECTOR

(MALE)

M2Si4410DY

Z1*R310k

R210k

R110k

R810k

R436k

R710k

μPLOGIC

RESET

SHORT

SHORT

LAST BLADE OR PIN ON CONNECTOR

SHORT

CX0.1μF

BACKPLANECONNECTOR

(FEMALE)

Q1

Q2

LAST BLADE OR PIN ON CONNECTOR

Z1 = 1SMA10A OR SMAJ10AM1: 2N7002LT1Q1, Q2: MMBT3904LT1* OPTIONAL

Figure 15. Connection Sense with ON/OFF Control

Figure 16. Connection Sense for Rocking the Daughter Board Back and Forth

LTC4211

274211fb


+

VCC SENSE

LTC4211

8

2

3 4

7 6

CLOAD

VOUT12V3A

GND4211 F17

5

1

R412.4k

GATE

GNDTIMER

PCB CONNECTION SENSE CTIMER8.2nF

FB

ONSHORT

LONGVCC12V

GNDLONG

Z1 = 1SMA12A OR SMAJ12A** HIGHLY RECOMMENDED

RESETR210k

R161.9k

RX10Ω

RSENSE0.012Ω

PCB EDGECONNECTOR

(MALE) M1Si4410DY

Z1** RG100Ω

R393.1k

R510k

μPLOGIC

RESET

CX100nF

BACKPLANECONNECTOR

(FEMALE)

12V Hot Swap Application

Figure 17 shows a 12V, 3A Hot Swap application circuit. The resistor divider R1/R2 programs the undervoltage lockout externally and allows the system to start up after VCC increases above 9.46V. The resistor divider R3/R4 monitors VOUT and signals the RESET pin when VOUT goes above 10.54V. Transient voltage suppressor Z1 and snubber network (CX, RX) are highly recommended to protect the 12V applications system from ringing and voltage spikes. RG is recommended for VCC > 10V and it can minimize high frequency parasitic oscillations in the power MOSFET.

AUTORETRY AFTER A FAULT

To configure the LTC4211 to automatically retry after a fault condition, the FAULT and ON pins can be connected to a pull-up resistor (RAUTO) to the supply, as shown in

Figure 17. 12V Hot Swap Application

Figure 18. In this case, the autoretry circuitry will attempt to restart the LTC4211 with a 50% duty cycle, as shown in the timing diagram of Figure 19. To prevent overheat-ing the external MOSFET and other components during the autoretry sequence, adding a capacitor (CAUTO) to the circuit introduces an RC time constant (tOFF) that adjusts the autoretry duty cycle. Equation 14 gives the autoretry duty cycle, modified by this external time constant:

Autoretry Duty Cycle ≈ tTIMER

tOFF + 2 • tTIMER• 100%

(14)

where tTIMER = LTC4211 system timing(see TIMER func-tion) and tOFF is a time needed to charge capacitor CAUTO from 0V to the ON pin threshold (1.316V).

In Figure 18 with RAUTO = 1M, the external RC time constant is set at 1 second, the tTIMER delay equals 6.2ms and the autoretry duty cycle drops from 50% to 2.5%.

Figure 18. LTC4211MS Autoretry Application

FAULT

VCC

LTC4211MS

SENSE

GATE

FB

1

2

3

4

5

10

RSENSE0.007Ω

Q1Si4410DY

9

8

7

6

RESET

ON

FILTER

TIMER

CTIMER10nF

GND

CFILTER100pF

RAUTO(SEE NOTE)

RPULL-UP10k

CAUTO1μF

R310Ω

Z1*

NOTE:Q1 MOUNTED TO 300mm2 COPPER AREA

RAUTO = 1M YIELDS 2.5%DUTY CYCLE AND Q1 TCASE = 50°C

RAUTO = 3.2M YIELDS 0.8%DUTY CYCLE AND Q1 TCASE = 37°C


4211 F18

C10.1μF

R136k

VOUT5V5A

CLOAD

R215k

+

LONGVCC5V

GND

RESET

LONG

PCB EDGECONNECTOR

(MALE)

BACKPLANECONNECTOR

(FEMALE)

SHORT

LTC4211

284211fb


1

VCC

TIMER

GATE

RESET

VCC – VSENSE

FILTER

VOUT

2 3 5 6 74 B8



tOFF t1 t2 tFILTER tOFF

VREF

>50mV

GATE

VFB < VREFVOUT

FPD

tRESET

VSENSE = 50mV

REGULATEDLOAD CURRENT

10μA

4211 F19

2μA

ON/FAULTON/FAULT

DUTY CYCLE = (tFILTER << t1, t2 AND tOFF)t2

tOFF + t1 + t2

To increase the RC delay, the user may either increase CAUTO or RAUTO. However, increasing CAUTO > 2μF will actually limit the RC delay due to the reset sink-current capability of the FAULT pin. Therefore, in order to increase the RC delay, it is more effective to either increase RAUTO or to put a bleed resistor in parallel with CAUTO to GND. For example, increasing RAUTO in Figure 18 from 1M to 3.2M decreases the duty cycle to 0.8%.

HOT SWAPPING TWO SUPPLIES

Using two external pass transistors, the LTC4211 can switch two supply voltages. In some cases, it is necessary to bring up the dominant supply first during power-up but ramp them down together during the power-down phase. The circuit in Figure 20 shows how to program two dif-ferent delays for the pass transistors. The 5V supply is powered up first. R1 and C3 are used to set the rise and fall times on the 5V supply. Next, the 3.3V supply ramps

up with 20ms delay set by R6 and C2. On the falling edge, both supplies ramp down together because D1 and D2 bypass R1 and R6.

OVERVOLTAGE TRANSIENT PROTECTION

Good engineering practice calls for bypassing the supply rail of any analog circuit. Bypass capacitors are often placed at the supply connection of every active device, in addition to one or more large value bulk bypass capacitors per sup-ply rail. If power is connected abruptly, the large bypass capacitors slow the rate of rise of the supply voltage and heavily damp any parasitic resonance of lead or PC track inductance working against the supply bypass capacitors.

The opposite is true for LTC4211 Hot Swap circuits mounted on plug-in cards. In most cases, there is no supply bypass capacitor present on the powered supply voltage side of the MOSFET switch. An abrupt connection, produced by

Figure 19. Autoretry Timing

LTC4211

294211fb


1

2

3

4

8

7

6

5

VCC

SENSE

GATE

FB

RESET

ON

TIMER

GND

LTC4211

4211 F20

D11N4148D2

1N4148

Q11/2 Si4936DY

Q21/2 Si4936DY

R20.015Ω

5%

R310Ω5%

R810ΩZ1*

C40.1μF

C110nF16V

R110k5%

R61M5%

R710Ω5%

R42.74k1%

TRIP POINT: 4.06V

R51.2k1%

C30.047μF25V

C20.022μF25V

CLOAD

CLOADD3**

VOUT13.3V2A

VOUT25V2A

5V OUT3.3V OUT

CURRENT LIMIT: 3.3A

+

+R910Ω

R1010k

10kZ2*

C50.1μF

R1110k

LONG3.3V

GND

RESET

LONG

**D3 IS OPTIONAL AND HELPS DISCHARGE VOUT1 IF VOUT2 SHORTS

PCB EDGECONNECTOR

(MALE)

LONG

BACKPLANECONNECTOR

(FEMALE)

5V

SHORT

SHORTON

Z1, Z2: 1SMA10A OR SMAJ10A* OPTIONAL

+VCC SENSE

LTC4211

8

34

7 6

COUT

VOUT5V5A

OUTPUTGND

INPUTGND

4211 F21

5

1

2

R215k

GATE

GND TIMER

CTIMER

FB

ON ON

RESET

RX10Ω

VIN5V

RSENSE0.007Ω

Q1Si4410DY

R136k

RESET

Z1*

CX0.1μF


inserting the board into a backplane connector, results in a fast rising edge applied on the supply line of the LTC4211.

Since there is no bulk capacitance to damp the para-sitic track inductance, supply voltage transients excite parasitic resonant circuits formed by the power MOSFET capacitance and the combined parasitic inductance from the wiring harness, the backplane and the circuit board traces.

In these applications, there are two methods that should be applied together for eliminating these supply voltage transients: using transient voltage suppressor to clip the transient to a safe level and snubber networks. Snubber networks are series RC networks whose time constants are experimentally determined based on the board’s parasitic resonance circuits. As a starting point, the capacitors in these networks are chosen to be 10× to 100× the power MOSFET’s COSS under bias. The series resistor is a value determined experimentally and ranges from 1Ω to 50Ω, depending on the parasitic resonance circuit. For applica-tions with supply voltages of 12V or higher the ringing and overshoot during hot-swapping or when the output is short-circuited can easily exceed the absolute maximum specification of the LTC4211. To reduce the danger, tran-sient voltage suppressors and snubber networks are highly recommended. For applications with lower supply voltages such as 5V, usually a snubber is adequate to reduce the

supply ringing, although a transient voltage suppressor may be required for inductive and high current applications. Note that in all LTC4211 5V applications schematics, tran-sient suppressor and snubber networks have been added for protection. The transient suppressor is optional and a simple short-circuit test can be performed to determine if it is necessary. These protection networks should be mounted very close to the LTC4211’s supply input rail using short lead lengths to minimize lead inductance. This is shown in Figure 21, and a recommended layout of the transient protection devices around the LTC4211 is shown in Figure 22.

Figure 20. Switching 5V and 3.3V

Figure 21. Placing Transient Protection Devices Close to the LTC4211’s Input Rail

LTC4211

304211fb


RES

ET

ON

TIM

ER

GN

D

VC

C

SEN

SE

LTC4211**

1

4211 F22

GA

TE

FB

D

D

D

D

G

S

S

S

W

CURRENT FLOWTO LOAD

CURRENT FLOWTO LOAD

CURRENT FLOWFROM LOAD

SENSE RESISTOR(RSENSE)

POWER MOSFET(SO-8)

W

W

VIA TOGND PLANE

NOTES:DRAWING IS NOT TO SCALE!*OPTIONAL COMPONENTS**ADDITIONAL DETAILS OMITTED FOR CLARITY

R415k

CTIMER10nF

R336k

CGX*RGX*

RX

CX

SNUBBERNETWORK

Z1*TRANSIENTVOLTAGESUPPRESSOR

Figure 22. Recommended Layout for LTC4211 Protection Devices, RSENSE, Power MOSFET and Feedback Network

LTC4211

314211fb


1

2

3

4

5

10

9

8

7

6

FAULT

VCC

SENSE

GATE

FB

RESET

ON

FILTER

TIMER

GND

LTC4211

Z1 = 1SMA10A OR SMAJ10AZ2 = 1N4691* OPTIONAL

Q1Si4410DY

R136k

VOUT5V5A

R215k

CLOAD

4211 F23

RSENSE0.007Ω

+

CTIMER10nF

CFILTER47pF

Z26.2V

LONG5V

GND

FAULT

LONG

PCB EDGECONNECTOR

(MALE)

BACKPLANECONNECTOR

(FEMALE)

SHORT

SHORT

SHORTRESET

ON/OFF

R310ΩZ1*

C10.1μF

R510k

R610k

R710k

R410k

SUPPLY OVERVOLTAGE DETECTION/PROTECTION USING FILTER PIN

In addition to using external protection devices around the LTC4211 for large scale transient protection, low power Zener diodes can be used with the LTC4211’s FILTER pin to act as a supply overvoltage detection/protection circuit on either the high side (input) or low side (output) of the external pass transistor. Recall that internal control circuitry keeps the LTC4211 GATE voltage from ramping up if VFILTER > 1.156V, or when an external fault condition (VFILTER > 1.236V) causes FAULT to be asserted low.

High Side (Input) Overvoltage Protection

As shown in Figure 23, a low power Zener diode can be used to sense an overvoltage condition on the input (high) side of the main 5V supply. In this example, a low bias current 1N4691 Zener diode is chosen to protect the system. Here, the Zener diode is connected from VCC to the LTC4211’s FILTER pin (Pin 3 MS). If the input volt-age to the system is greater than 6.8V during start-up, the voltage on the FILTER pin is pulled higher than its 1.156V threshold. As a result, the GATE pin is not allowed to ramp and the second timing cycle will not commence until the supply overvoltage condition is removed. Should the supply overvoltage condition occur during normal

operation, internal control logic would trip the electronic circuit breaker and the GATE would be pulled to ground, shutting OFF the external pass transistor. If a lower supply overvoltage threshold is desired, use a Zener diode with a smaller breakdown voltage.

A timing diagram for illustrating LTC4211 operation under a high side overvoltage condition is shown in Figure 24. The start-up sequence in this case (between Time Points 1 and 2) is identical to any other start-up sequence under normal operating conditions. At Time Point 2A, the input supply voltage causes the Zener diode to conduct thereby forcing VFILTER > 1.156V. At Time Point 3, FAULT is asserted low and the TIMER pin voltage ramps down. At Time Point 4, the LTC4211 checks if VFILTER < 1.156V. FAULT is asserted low (but not latched) to indicate a start-up failure. The start-up sequence only resumes with the second timing cycle at Time Point 5 when the input overvoltage condition is removed. At this point in time, the GATE pin voltage is allowed to ramp up, FAULT is pulled to logic high and the circuit breaker is armed. At any time after Time Point 5, should a supply overvoltage condition develop (VFILTER > 1.236V), the electronic circuit breaker will trip, the GATE will be pulled low to turn off the external MOSFET and FAULT will be asserted low and latched. This sequence is shown in detail at Time Point B.

Figure 23. LTC4211MS High Side Overvoltage Protection Implementation

LTC4211

324211fb


1

VCC ON

TIMER

GATE

RESET

FILTER

>VREF – 80mV

FAULT

VOUT

GATE

VOUT

2 3 5 6 72A 4 8 A B C

SLOW COMPARATOR ARMEDIF OVERVOLTAGE GOESAWAY, SECOND CYCLE

CONTINUESOVERVOLTAGE

IF ANY FAULT HAPPENSAFTER THIS POINT, THE CIRCUIT BREAKER TRIPS AND FAULT LATCHES LOW

OVERVOLTAGE CIRCUIT BREAKERTRIPS, GATE PULLS DOWN ANDFAULT LATCHES LOW

FAULT IS PULLED LOW (BUT NOT LATCHED) DUE TO A START-UP OVERVOLTAGE PROBLEM


POWER BADVFB < VREF

FPD

4211 F24

>VREF

FAULT LATCHED LOW

Low Side (Output) Overvoltage Protection

A Zener diode can be used in a similar fashion to detect/protect the system against a supply overvoltage condition on the load (or low) side of the pass transistor. In this case, the Zener diode is connected from the load to the LTC4211’s FILTER pin, as shown in Figure 25. An additional diode, D1, prevents the FILTER pin from pulling low during an output short-circuit. Figure 26 illustrates the timing

diagram for a low side output overvoltage condition. In this example, VCC starts up in an overvoltage condition but the LTC4211 can only sense the overvoltage supply condition at Time Point 6 when the GATE pin has ramped up. At Time Point 6, VFILTER is greater than 1.236V, the circuit breaker is tripped, the GATE pin voltage is pulled to ground and FAULT is asserted low and latched.

Figure 24. High Side Overvoltage Protection

LTC4211

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1

2

3

4

5

10

9

8

7

6

FAULT

VCC

SENSE

GATE

FB

RESET

ON

FILTER

TIMER

GND

LTC4211

Q1Si4410DY

R136k

VOUT5V5A

R215k

CLOAD

4211 F25

RSENSE0.007Ω

+

CTIMER10nF

CFILTER47pF

Z26.2V

LONG5V

GND

FAULT

LONG

PCB EDGECONNECTOR

(MALE)

BACKPLANECONNECTOR

(FEMALE)

SHORT

SHORT

SHORTRESET

ON/OFF

R410ΩZ1*

C10.1μF

R510k

R710k

R610k

R310k

Z1 = 1SMA10A OR SMAJ10AZ2 = 1N4691* OPTIONAL

D1IN4148

1 2 3 4 5

OVERVOLTAGE SENSED BY FILTER PIN AND CIRCUIT BREAKER TRIPS

VCC

TIMER

GATE

VOUT

RESET

FILTER

ON

6

FAULT

FPD

4211 F26

VREF

Figure 25. LTC4211MS Low Side Overvoltage Protection Implementation

Figure 26. Low Side Overvoltage Protection

LTC4211

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APPLICATIONS INFORMATIONIn either case, the LTC4211 can be configured to au-tomatically initiate a start-up sequence. Please refer to the section on AutoRetry After a Fault for additional information.

PCB Layout Considerations

For proper operation of the LTC4211’s circuit breaker function, a 4-wire Kelvin connection to the sense resis-tors is highly recommended. A recommended PCB layout for the sense resistor, the power MOSFET and the GATE drive components around the LTC4211 is illustrated in Figure 22. In Hot Swap applications where load currents can reach 10A or more, narrow PCB tracks exhibit more resistance than wider tracks and operate at more elevated temperatures. Since the sheet resistance of 1 ounce cop-

per foil is approximately 0.54mΩ/square, track resistances add up quickly in high current applications. Thus, to keep PCB track resistance and temperature rise to a minimum, PCB track width must be appropriately sized. Consult Ap-pendix A of LTC Application Note 69 for details on sizing and calculating trace resistances as a function of copper thickness.

In the majority of applications, it will be necessary to use plated-through vias to make circuit connections from component layers to power and ground layers internal to the PC board. For 1 ounce copper foil plating, a good starting point is 1A of DC current per via, making sure the via is properly dimensioned so that solder completely fills any void. For other plating thicknesses, check with your PCB fabrication facility.

LTC4211

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APPENDIXTable 4 lists some current sense resistors that can be used with the circuit breaker. Table 5 lists some power MOSFETs that are available. Table 6 lists the web sites of several

manufacturers. Since this information is subject to change, please verify the part numbers with the manufacturer.

Table 4. Sense Resistor Selection Guide

CURRENT LIMIT VALUE PART NUMBER DESCRIPTION MANUFACTURER

1A LR120601R050 0.05Ω 0.5W 1% Resistor IRC-TT

2A LR120601R025 0.025Ω 0.5W 1% Resistor IRC-TT

2.5A LR120601R020 0.02Ω 0.5W 1% Resistor IRC-TT

3.3A WSL2512R015F 0.015Ω 1W 1% Resistor Vishay-Dale

5A LR251201R010F 0.01Ω 1.5W 1% Resistor IRC-TT

10A WSR2R005F 0.005Ω 2W 1% Resistor Vishay-Dale

Table 5. N-Channel Selection Guide

CURRENT LEVEL (A) PART NUMBER DESCRIPTION MANUFACTURER

0 to 2 MMDF3N02HD Dual N-Channel SO-8RDS(ON) = 0.1Ω, CISS = 455pF

ON Semiconductor

2 to 5 MMSF5N02HD Single N-Channel SO-8RDS(ON) = 0.025Ω, CISS = 1130pF

ON Semiconductor

5 to 10 MTB50N06V Single N-Channel DD PakRDS(ON) = 0.028Ω, CISS = 1570pF

ON Semiconductor

10 to 20 MTB75N05HD Single N-Channel DD PakRDS(ON) = 0.0095Ω, CISS = 2600pF

ON Semiconductor

Table 6. Manufacturers’ Web Sites

MANUFACTURER WEB SITE

TEMIC Semiconductor www.temic.com

International Rectifier www.irf.com

ON Semiconductor www.onsemi.com

Harris Semiconductor www.semi.harris.com

IRC-TT www.irctt.com

Vishay-Dale www.vishay.com

Vishay-Siliconix www.vishay.com

Diodes, Inc. www.diodes.com

LTC4211

364211fb

PACKAGE DESCRIPTIONPlease refer to http://www.linear.com/designtools/packaging/ for the most recent package drawings.

MSOP (MS8) 0307 REV F

0.53 0.152

(.021 .006)

SEATINGPLANE

NOTE:1. DIMENSIONS IN MILLIMETER/(INCH)2. DRAWING NOT TO SCALE3. DIMENSION DOES NOT INCLUDE MOLD FLASH, PROTRUSIONS OR GATE BURRS. MOLD FLASH, PROTRUSIONS OR GATE BURRS SHALL NOT EXCEED 0.152mm (.006") PER SIDE4. DIMENSION DOES NOT INCLUDE INTERLEAD FLASH OR PROTRUSIONS. INTERLEAD FLASH OR PROTRUSIONS SHALL NOT EXCEED 0.152mm (.006") PER SIDE5. LEAD COPLANARITY (BOTTOM OF LEADS AFTER FORMING) SHALL BE 0.102mm (.004") MAX

0.18

(.007)

0.254

(.010)

1.10

(.043)MAX

0.22 – 0.38

(.009 – .015)TYP

0.1016 0.0508

(.004 .002)

0.86

(.034)REF

0.65

(.0256)BSC

0 – 6 TYP

DETAIL “A”

DETAIL “A”

GAUGE PLANE

1 2 3 4

4.90 0.152

(.193 .006)

8 7 6 5

3.00 0.102

(.118 .004)

(NOTE 3)

3.00 0.102

(.118 .004)

(NOTE 4)

0.52

(.0205)REF

5.23(.206)MIN

3.20 – 3.45(.126 – .136)

0.889 0.127(.035 .005)

RECOMMENDED SOLDER PAD LAYOUT

0.42 0.038(.0165 .0015)

TYP

0.65(.0256)

BSC

MS8 Package8-Lead Plastic MSOP

(Reference LTC DWG # 05-08-1660 Rev F)

LTC4211

374211fb


MSOP (MS) 0307 REV E

0.53 ± 0.152

(.021 ± .006)

SEATINGPLANE

0.18

(.007)

1.10

(.043)MAX

0.17 – 0.27

(.007 – .011)

TYP

0.86

(.034)REF

0.50

(.0197)BSC

1 2 3 4 5

4.90 ± 0.152

(.193 ± .006)

0.497 ± 0.076

(.0196 ± .003)

REF8910 7 6

3.00 ± 0.102

(.118 ± .004)

(NOTE 3)

3.00 ± 0.102

(.118 ± .004)

(NOTE 4)

NOTE:1. DIMENSIONS IN MILLIMETER/(INCH)2. DRAWING NOT TO SCALE3. DIMENSION DOES NOT INCLUDE MOLD FLASH, PROTRUSIONS OR GATE BURRS. MOLD FLASH, PROTRUSIONS OR GATE BURRS SHALL NOT EXCEED 0.152mm (.006") PER SIDE4. DIMENSION DOES NOT INCLUDE INTERLEAD FLASH OR PROTRUSIONS. INTERLEAD FLASH OR PROTRUSIONS SHALL NOT EXCEED 0.152mm (.006") PER SIDE5. LEAD COPLANARITY (BOTTOM OF LEADS AFTER FORMING) SHALL BE 0.102mm (.004") MAX

0.254

(.010)0° – 6° TYP

DETAIL “A”

DETAIL “A”

GAUGE PLANE

5.23(.206)MIN

3.20 – 3.45(.126 – .136)

0.889 ± 0.127(.035 ± .005)


0.305 ± 0.038(.0120 ± .0015)

TYP

0.50(.0197)

BSC

0.1016 ± 0.0508

(.004 ± .002)

MS Package10-Lead Plastic MSOP

(Reference LTC DWG # 05-08-1661 Rev E)

LTC4211

384211fb


.016 – .050

(0.406 – 1.270)

.010 – .020

(0.254 – 0.508) 45

0 – 8 TYP.008 – .010

(0.203 – 0.254)

SO8 REV G 0212

.053 – .069

(1.346 – 1.752)

.014 – .019

(0.355 – 0.483)TYP

.004 – .010

(0.101 – 0.254)

.050

(1.270)BSC

1 2 3 4

.150 – .157

(3.810 – 3.988)

NOTE 3

8 7 6 5

.189 – .197

(4.801 – 5.004)NOTE 3

.228 – .244

(5.791 – 6.197)

.245MIN .160 .005


.045 .005 .050 BSC

.030 .005 TYP

INCHES

(MILLIMETERS)

NOTE:1. DIMENSIONS IN

2. DRAWING NOT TO SCALE3. THESE DIMENSIONS DO NOT INCLUDE MOLD FLASH OR PROTRUSIONS. MOLD FLASH OR PROTRUSIONS SHALL NOT EXCEED .006" (0.15mm)4. PIN 1 CAN BE BEVEL EDGE OR A DIMPLE

S8 Package8-Lead Plastic Small Outline (Narrow .150 Inch)

(Reference LTC DWG # 05-08-1610 Rev G)

LTC4211

394211fb

Information furnished by Linear Technology Corporation is believed to be accurate and reliable. However, no responsibility is assumed for its use. Linear Technology Corporation makes no representa-tion that the interconnection of its circuits as described herein will not infringe on existing patent rights.

REVISION HISTORYREV DATE DESCRIPTION PAGE NUMBER

B 03/12 Updated Pin description information

Updated Figure 2 and supporting text

Moved Figure 7 and supporting text to page 16 and renumbered to Figure 6

Updated text under Second Timing (Soft-Start) Cycle

Replaced CGX with CGATE in Figure 6

Revised Figure 26 and supporting Low Side (Output) Overvoltage Protection text

10, 11

13

16

16

16

32, 33

(Revision history begins at Rev B)

LTC4211

404211fb

Linear Technology Corporation1630 McCarthy Blvd., Milpitas, CA 95035-7417 (408) 432-1900 ● FAX: (408) 434-0507 ● www.linear.com © LINEAR TECHNOLOGY CORPORATION 2006

LT 0312 REV B • PRINTED IN USA

RELATED PARTS

TYPICAL APPLICATIONLOW COST OVERVOLTAGE PROTECTION

There is an alternative method to implementing the over-voltage protection using a resistor divider at the FILTER pin (see Figures 27 and 28). In this implementation, the SLOW COMP is NULL in Normal Mode. Only the FAST

COMP circuit breaker is available and the current limit level is 150mV/RSENSE. During the soft-cycle, the inrush current servo loop is at 50mV/RSENSE. So, the heavy load should only turn on at/after the end of second cycle where the RESET pin goes high.

Figure 27. LTC4211MS High Side Overvoltage Protection Implementation(In Normal Mode, SLOW COMP Is Disabled. In Soft-Start Cycle, ISOFTSTART Is Still 50mV/RSENSE)

Figure 28. LTC4211MS Low Side Overvoltage Protection Implementation(In Normal Mode, SLOW COMP Is Disabled. In Soft-Start Cycle, ISOFTSTART Is Still 50mV/RSENSE)

1

2

3

4

5

10

9

8

7

6

FAULT

VCC

SENSE

GATE

FB

RESET

ON

FILTER

TIMER

GND

LTC4211

Q1Si4410DY

R13.6k

VOUT5V5A

R2750Ω

CLOAD

4211 F28

RSENSE0.007Ω

+

R8750Ω

CTIMER10nF

LONG5V

GND

FAULT

LONG

PCB EDGECONNECTOR

(MALE)

BACKPLANECONNECTOR

(FEMALE)

SHORT

SHORT

SHORTRESET

ON/OFF

R710ΩZ1*

C10.1μF

R410k

R610k

R510k

R310k


PART NUMBER DESCRIPTION COMMENTS

LTC1421 Two Channels, Hot Swap Controller 24-Pin, Operates from 3V to 12V and Supports –12V

LTC1422 Single Channel, Hot Swap Controller 8-Pin, Operates from 2.7V to 12V

LT1640AL/LT1640AH Negative Voltage Hot Swap Controller 8-Pin, Operates from –10V to –80V

LT1641-1/LT1641-2 Positive Voltage Hot Swap Controller 8-Pin, Operates from 9V to 80V, Latch-Off/Auto Retry

LTC1642 Single Channel, Hot Swap Controller 16-Pin, Overvoltage Protection to 33V

LTC1644 PCI Hot Swap Controller 16-Pin, 3.3V, 5V and ±12V, 1V Precharge, PCI Reset Logic

LTC1647 Dual Channel, Hot Swap Controller 8-Pin, 16-Pin, Operates from 2.7V to 16.5V

LTC4230 Triple Hot Swap Controller with Multifunction Current Control Operates from 1.7V to 16.5V

1

2

3

4

5

10

9

8

7

6

FAULT

VCC

SENSE

GATE

FB

RESET

ON

FILTER

TIMER

GND

LTC4211

Q1Si4410DY

R136k

VOUT5V5A

R215k

CLOAD

4211 F27

RSENSE0.007Ω

+

CTIMER10nF

LONG5V

GND

FAULT

LONG

PCB EDGECONNECTOR

(MALE)

BACKPLANECONNECTOR

(FEMALE)

SHORT

SHORT

SHORTRESET

ON/OFF

R310ΩZ1*

C10.1μF

R510k

R610k

R84.3k

R710k

R9750Ω

R410k


ltc4211 - hot swap controller with multifunction …ltc4211 1 4211fb typical application features...

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