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7 Communication Systems
. . . transmitting messages, and possibly information . . .
Transformationof source (message) signalx(t)into transmit signal
y(t)matchedto transmission channel (frequency range, propagation
and attenuation characteristics etc.)
Mechanisms
Modulation process of embedding information-bearing signal
x(t)into y(t)
Demodulation process of extracting information-bearing sig-
nal
Multiplexing combination of independent source signals into
a composite signal suitable for transmission over a common
channel
Distinguish
Analog vs. digital message signals
analog time continuous + continuum of values digital time-discrete+ quantized values
Analog vs. digital transmission
Transmit signal varies continuously with message signal
Finiteset of transmit signals to represent information This chapter
Analog transmission of analog message signals
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Outline
7.1 Amplitude Modulation
7.2 Frequency Modulation7.3 Analog-Pulse Amplitude Modulation
7.4 Multiplexing
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7.1 Amplitude Modulation
Amplitude modulation (AM):Amplitudeofsinusoidal carrier signal
c(t)is varied in proportion to a message signal x(t)
AM is oldest and most simple technique for wireless transmission
and multiplexing.
Used for longwave, mediumwave, and shortwave radio and broad-
casting, for analog television, for frequency multiplexing for analog
telephone transmission, etc.
7.1.1 Modulation
Distinguish
Double-sideband AM
AM with/suppressed carrier
Quadrature AM
Single-sideband AM
Vestigial-sideband AM
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Double-sideband AM suppressed carrier
Generation of AM wave
y(t) =x(t)c(t) =x(t)
2crmscos(ct + c)with carrier signal
c(t) =
2crmscos(ct + c)
Notation
x(t): message signal, modulating signal
y(t): modulated signal c(t): carrier signal, carrier wave crms: root mean square value of sinusoidal carrier c: carrier frequency c: carrier phase
Illustration 2crmscos(ct + c)
x(t) y(t)
y(t)x(t)
t t
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Frequency domain
Spectrum of carrier waveC(j) =
2crms (
c)ejc + (+ c)e
jc Multiplication property of Fourier transformY(j) =
crms2
X(j( c))ejc +X(j(+ c))ejc
Replications of original spectrum centered aroundc
double representation of modulation signal
Bandwidthof message signal M bandwidth of modulatedsignal2
M x(t)recoverable fromy(t)only ifc> M
0
0
2crms
2crms
cc
c c c+ M
X(j)
C(j)
Y(j)
1
c M
sidebandsidebandUpper
sidebandsideband
UpperLower Lower
MM
crms2
0
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Double-sideband AM with carrier
Add carrier wave to transmit signal
Simple demodulation possible
Less power efficient, since carrier does not contain informa-tion
Modulated signal
y(t) = (A + x(t))
2crmscos(ct + c)
with
DC component A Modulation indexm=
max{|x(t)|}A
Illustration
Phase reversals
m >1
m= 1
m
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Efficiency factor
= average power of message signal
average total power
= m2S21 + m2S2
with degree of saturation
S=
average power of message signal
max{|x(t)|} Frequency domain
Superposition of message signal part and carrier waveY(j) =
crms2
X(j( c))ejc + X(j(+ c))ejc
+
2Acrms
( c)ejc + (+ c)ejc
0
X(j)
1
0c c
Y(j)
2Acrms
2Acrms
Uppersidebandsideband sideband
Lower Lower Uppersideband
crms2
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Quadrature AM
Feature
2
doubled-sideband AM using orthogonal carrier waves
cos(ct)and sin(ct)
Twoindependentmessage signals occupy same transmis-sion bandwidth (multiplexing)
Bandwidth-conservation scheme
Time-domain description (c= 0)
y(t) =
2crms(x1(t)cos(ct) x2(t)sin(ct))
Block diagram
2crmssin(ct)
2crmscos(ct)
y(t)
x2(t)
x1(t)
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Frequency domain
Spectrum of modulated signalY(j) =
crms
2 X1(j( c)) + X1(j(+c))+j
X2(j( c))X2(j(+ c))
Spectrum ofY(j) not symmetric about c no doublerepresentation
Bandwidthof modulated signal2Mequals sum of the band-
widths of the modulation signals nobandwidth expansion Illustration for real-valued spectra X1(j)andX2(j)
Im{Y(j)}
c
c
Re{Y(j)}
X2(j)
X1(j)
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Single-sideband AM
Observation from double-sideband AM
Redundant representation of message signal in upper and
lower sideband
Twice the signal bandwidth M is required
Therefore
No information lost if one sideband is suppressed!single-sideband AM
Frequency-domain description
2crms
0
X(j)
1
0c c
Y(j)
Upper sideband
Lower sideband
0c c
Y(j)
2crms
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Spectrum (c= 0)
Upper sidebandY(j) =
2crms1
2
(sign(
c) + 1) X(j(
c))
12
(sign(+ c) 1) X(j(+ c))
Lower sidebandY(j) =
2crms
12
(sign(+ c) + 1) X(j(+ c))
1
2
(sign(
c)
1) X(j(
c))
Remark:
We note that from the convolution property of the Fourier transform
andF{1/t} = jsign()we have the Fourier pair1
x(t) 1
tF jX(j)sign().
The left-hand side operation is called Hilbert transform, and is de-fined as
H{x(t)} = 1
x(t) 1t
= 1
x()
t d
and thus
H{x(t)} = F1{jX(j)sign()}
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Single-sideband signal
Upper sidebandy(t) =
F1
{Y(j)
}= 2crms
12
(x(t) +jH{x(t)}) e+jct
+1
2(x(t)jH{x(t)}) ejct
y(t) =
2crms(x(t)cos(ct)H{x(t)}sin(ct))
Lower sidebandy(t) =
2crms(x(t)cos(ct) + H{x(t)}sin(ct))
Block diagram
x(t)
2crmssin(ct)
2crmscos(ct)y(t)
H{}
Observe
Single-sideband AM is QAM withx2(t) = H{x1(t)}
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Illustration for real-valued spectrumX(j)
Im
F{cos(ct)}
F{sin(ct)}
Re
+
Y(j)
Im
Re
Y(j)
Im
Re
=
Im
Re
++
Im
=
Re
Im Im
ReRe
Im
Re
X(j)
F{H{x(t)}} = jsign()X(j)
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Implementation of exact Hilbert-transform filter impossible
For DC-free message signals soft-Hilbert filter possible
Method by Weaver
0
X(j)
1
uo ou
y(t)
2crmscos(2t)
2crmssin(2t)
2cos(1t)
2sin(1t)x(t)
Lowpass
Lowpass
1
1
1= o+u
2
ou2
1
Lowpass
1= o+ u2
2=c 1
+ : upper sideband
: lower sideband
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Vestigial-sideband AM
Single-sideband modulation not applicable when message signal
contains significant low-frequency components, e.g., for televi-
sion signals
Compromise between double- and single-sideband AM
Vestigial-sideband AM One sideband is passed almost completely Onlyvestigeof other sideband is retained
Sideband-shaping filtersymmetric about c
Illustration
c
Y(j)
c+ Mc M
X(j)
MM
cc
Bandwidth-expansion factor (roll-off factor) [0, 1]
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7.1.2 Demodulation
Assumption: No overlap (c> M), transmitted signaly(t)is also
received signal (no noise, distortion etc.)
Distinguish
Synchronous demodulation
Asynchronous demodulation
Synchronous Demodulation
Demodulation of high-frequency signal into low-frequency signal
with locally generated carrier wave
c(t) =
2
crmscos(ct +
c)
Carrier frequency offset: c= c c Carrier phase offset: c=c c
Subsequent lowpass filtering with cutoff frequency co
Transmitter-receiver structure for general QAM
w2(t)
w1(t)
y(t)
2crmssin(ct + c)
2crmscos(ct + c)
x2(t)
x1(t)
v2(t)
v1(t)co
Lowpass
co
Lowpass
2crms sin(ct + c)
2
crmscos(ct +
c)
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Signals after multiplication with carrier
w1(t) = 2x1(t)cos(ct + c)cos(ct +
c)
2x2(t)sin(ct + c)cos(
ct +
c)
= x1(t) [cos(ct + c) +cos((c+ c)t + c+c)]+x2(t) [sin(ct + c) sin((c+c)t + c+ c)]
w2(t) = 2x2(t)sin(ct + c)sin(ct +
c)
2x1(t)cos(ct + c)sin(ct + c)= x2(t) [cos(ct + c) cos((c+ c)t +c+ c)]x1(t) [sin(ct + c) +sin((c+c)t + c+ c)]
Signals after lowpass filtering with
M< oc 2c M
v1(t) = x1(t)cos(ct + c) + x2(t)sin(ct + c)
v2(t) = x2(t)cos(ct + c) x1(t)sin(ct + c)
Convenient combination to complex demodulated signal
v1(t) +jv2(t) = x1(t) [cos(ct + c) jsin(ct + c)]+jx2(t) [cos(ct + c) jsin(ct + c)]
v1(t) +jv2(t) = (x1(t) +jx2(t))ej(ct+c)
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Double-sideband AM:x1(t) =x(t), x2(t) 0 Only real part used
v(t) =v1(t) =x(t)cos(ct + c)
Forv(t) = x(t)c= 0andc=k , k ZZ
Synchronous carriers required!
In case of AM with carrier: highpass to suppress carrier
QAM
v1(t) = x1(t)cos(ct + c) + x2(t)sin(ct + c)
v2(t) = x2(t)cos(ct + c) x1(t)sin(ct + c) c= 0 andc =k , k ZZ: Coupling of signals
c= 0 andc=k , k ZZ: Separation of signals Single-sided AM: x1(t) =x(t), x2(t) = H{x(t)} Only real part used
v(t) = v1(t) =Re
(x(t)jH{x(t)})ej(ct+c)
= x(t)cos(ct + c)
H{x(t)
}sin(ct + c)
c= 0, phase offset:v(t) =x(t)cos(c)H{x(t)}sin(c)
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Frequency offset
Lowpass|W(j)|
c> c
Upper sideband |Y(j)|
cc
Lowpass|W(j)
|
c< c
Lower sideband
|W(j)|Lowpass
c> c
|Y(j)|
cc
Lowpass|W(j)
|
c< c
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Asynchronous Demodulation
No demodulation with carrier wave no need for synchroniza-tion
Evaluation ofenvelopeof received signal envelope detector Only applicable for Double-sideband AMwithcarrier andm 1
y(t)
t
2crms(A + x(t))
How to get rid of carrier wave?
For non-overlapping sidebands
H{y(t)} = H{(A +x(t)) 2crmscos(ct + c)}= (A + x(t)) 2crmssin(ct + c)
cos2(ct +c) +sin2(ct + c) = 1
env{y(t)} = 12y2(t) + H2{y(t)}
Envelopeenv{y(t)} = crms|A + x(t)|
m1= crms(A + x(t))
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Envelope detector
Hv(t): Bandpass filter to suppress DC component and highfrequencies|| > M
Non-overlapping sidebands andm 1 v(t) =x(t)
()/2
()2
y(t) Hv(j) v(t)
()2
H{}
Practical implementation
v(t)v(t)
y(t)
y(t) v(t) v(t)
ttt
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7.2 Frequency Modulation
Belongs to class ofangle modulation techniques
Representation of message in phaseof carrier wave
Average power= maximum power
zero dynamic of envelope efficient power amplification
Higher quality than amplitude modulation
higher power efficiency than amplitude modulation Requires higher bandwidth than amplitude modulation
trade-off between power and bandwidth efficiency Angle-modulated signal
y(t) =
2crmscos(ct + (t))
with information bearing phase (t)
Instantaneous frequency
i(t) =c+d(t)
dt
Types of angle modulation
Phase modulation (PM)
(t) =kpx(t)
Frequency modulation (FM)
i(t) c=kfx(t)(x(t): modulating signal)
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Frequency modulation
Modulated signal
y(t) = 2crmscosct +
t
(i() c) d
with
i(t) c=kfx(t)
Phase signal
(t) =kft
x() d
Maximum frequency deviation
=kfmax{|x(t)|}
kf issystem parameter Usually max{|x(t)|}adjusted through limiter is sys-
tem parameter
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Example:
Cosine message signal
x(t) =Acos(Mt) =kfA
i(t) c= cos(Mt) (t) = Msin(Mt)
FM signal
y(t) = 2crmscosct +Msin(Mt)(= PM signal with x(t) =Asin(Mt) andkp=kf/A)
t
t
t
y(t)
y(t)
x(t)
PM
FM
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Spectrum of FM signals for cosine signal x(t)
y(t) =
2crmscosct +
Msin(Mt)
= crms2
y(t)ejct + (y(t)ejct)
with
y(t) =ejM
sin(Mt)
y(t)periodic with period 2/M
Fourier series description ofyt)
y(t) =
k=Jk
M
ejkMt
with Bessel function of the first kind,nth order
Jk(u) = 1
2
ej(usin(v)kv) dv
Spectrum ofy(t)
Y(j) = 2
k=Jk
M
( kM)
Spectrum of FM signal
Y(j) =crms
2[Y(j( c)) + Y(j( c))]
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Illustration
0 2 4 6 8 10 12 14 160.5
0
0.5
1
6 4 2 0 2 4 60.4
0.2
0
0.2
0.4
u
J0(u)
J1(u) J2(u)
Y(j)
/M= 5
/M
J0(5)
J1(5)
J2(5)J2(5)
Interpretation:
Discrete spectrum LargerM density decreases Larger for fixedM bandwidth increases /M 1:
J0(/M) = 1, J1(/M) (/M)/2,Jk(/M) 0 fork >1
Spectrum ofnarrowbandFM similar to double-sideband
AM with carrier
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15 10 5 0 5 10 150
0.2
0.4
0.6
0.8
15 10 5 0 5 10 150
0.05
0.1
0.15
0.2
0.25
0.3
15 10 5 0 5 10 150
0.1
0.2
0.3
0.4
0.5
0.6
15 10 5 0 5 10 150
0.05
0.1
0.15
0.2
0.25
0.3
15 10 5 0 5 10 150
0.1
0.2
0.3
0.4
0.5
15 10 5 0 5 10 150
0.1
0.2
0.3
0.4
15 10 5 0 5 10 15
0
0.1
0.2
0.3
0.4
15 10 5 0 5 10 15
0
0.1
0.2
0.3
0.4
0.5
0.6
M
for
=
2
(5kHz)
forM
=
2
(1kHz)
= 2 (5kHz)
M= 20
M= 10
M= 2.5
M= 5
M= 5
M= 3.8
M= 2.4
M= 1
M= 2 (1 kHz)
/(2(1kHZ))/(2(1kHZ))
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Estimation of bandwidth of FM signal for cosine message signal
Strictly speaking: infinite bandwidth
Approximation by Carson
How many discrete spectral components are required to re-tainp (100%) of the total modulated signal power?Parseval:
J20(u) + 2
Kk=1
J2k(u) p
Bandwidth limited toB = 2KM
causes loss of(1p) (100%) in signal powerCarsons approximation of bandwidth of FM signal
B =
2(+ M) forp= 0.9
2(+ 2M) forp= 0.99
Note: bandwidth measured in Hz (as usual)Bf=B/(2)[Hz]
Carsons approximation is also applicable to non-cosine message
signals.
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Demodulation
Ideal angle modulation track angle of modulated signal
v(t) = v1(t) +jv
2(t) =
|v(t)
|ej(t)
v(t) = d
dt(arg{v(t)}) = d
dt
tan1
v2(t)
v1(t)
= kfx(t)
Lowpass
Lowpass
arg{}
v1(kT)
v2(kT)
2crms
cos(ct)
2
crmssin(ct)
y(t)
T
+ v(kT)
FM-AM conversion
v(t) = d
dt
y(t)
2crms
= (c+ kfx(t)) sin(ct + (t))
and AM envelope detector (c =kfmax{|x(t)|})
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7.3 Analog Pulse-Amplitude Modulation
Analog transmission of discrete-time sample valuesof message sig-
nal
Amplitude of the pulse carrier is modulated in accordance with in-
stantaneous sample values of the message signal.
Pulse-Amplitude Modulation (PAM)
Lowpass anti-aliasing filtering of message signal band limitation to || M Sampling signal at rate T = 2/s,s>2M
Modulation of impulses h(t)
x(nT)x(t)
Mx(t)
Lowpass
h(t) y(t)
PAM signal
y(t) =
n=x(nT)h(t nT))
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Example:
Rectangular pulse of durationT0
h(t) =rect
t T0/2T0
y(t) =
n=x(nT)rect
t T0/2 nT
T0
T
x(t)
T0
y(t)
t
Sampling-and-hold operation with sampling period T and holddurationT0
Express PAM signal
y(t) =
x(t)
k=
(t kT) h(t)
Spectrum of PAM signal
Y(j) = 1
T
k=
X(j( ns))H(j)
whereH(j) = F{h(t)}
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Effect of pulse shape
E.g. h(t) =recttT0/2T0
F H(j) =T0sincT02 ejT0/2
ss
(Xj)
MM
sincT0
2
2
T02
T0
Frequency distortion
Shorter pulse duration
less distortion
Demodulation of PAM signal
Lowpass filter with cutoff frequencyM< co s M Compensate for distortion due to pulse shape
Hr(j)y(t) v(t)
E.g. for rectangular pulse shape
Hr(j) =
1
T0sinc(T0/(2))ej(TdT0) , || M
0,
|
| (s
M)
dont care, else
v(t) =x(t Td)(delay Td for causal filter)
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7.4 Multiplexing
Combination of independent message signals into a composite signal
suitable for transmission over a common channel
General structure
xI(t)
Channel
v1(t)
v2(t)
vI(t)Demultiplexer
......
x1(t)
x2(t)
Multiplexer
Basic types of multiplexing
1. Frequency-division multiplexing (FDM)
Individual signals are separated by allocating them to differ-
ent frequency bands.
Used with sinusoidal carrier-wave modulation
Examples:
Wired telephony and telegraphy Radio and TV broadcasting 1st generation (analog) cellular phone systems as the US
Advanced Mobile Phone Service (AMPS), the UK Total
Access Communications System (TACS), the German C-Netz
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2. Time-division multiplexing (TDM)
Individual signals are separated by allocating them to differ-
ent time slots within a sampling interval.
Used with (digital) pulse modulation Examples:
Digital Enhanced Cordless Telecommunications (DECT) 2nd generation digital cellular phone systems as Global
System for Mobile Communications (GSM), Digital-American
Mobile Phone Service (D-AMPS), and Personal Digital
Cellular (PDC)
3. Code-division multiplexing (CDM)
Individual signals are separated by assignment of different
codes to them.
Used with digital pulse modulation
Examples:
3rd generation mobile communication standards CDMA2000,
Universal Mobile Telecommunications System (UMTS)
4. Space-division multiplexing (SDM)
Individual signals are separated spatially.
Based on directed antennas
Examples:
GSM, UMTS
If the message signals correspond to different user which access the
same transmission medium, the above techniques are also referred
to asmultiple-accesstechniques (FDMA, TDMA, CDMA, SDMA).
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Illustration
Tim
e
Frequency
SDMCDM
Frequency
Tim
e
TDM
Tim
e
Frequency
Power
Power
Pow
er
FDM
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7.4.1 Frequency-Division Multiplexing
Multiplexing
Lowpass filtering of message signal no interference with othersignals sharing the common channel
Modulation
Shift the frequency ranges of signals so as to occupy mutuallyexclusive frequency intervals
Most widely used: single-sideband AM
Bandpass filter restrict the band of each modulated wave to itsprescribed range
Summation forms input to common channel
Modulator
Modulator
Modulator
... ...
Bandpass
Bandpass
Bandpass
x1(t) Lowpass
x2(t) Lowpass
xI(t) Lowpass
supply
Carrier
... ...
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Demultiplexing received signal
Bandpass filtering to extract the modulated signals correspond-
ing to their specific frequency range
Demodulation to recover the original signal
Lowpass filtering to reduce interference and noise
Carrier
...
supply
Demod.
Demod.
Demod.
vI(t)
...
v2(t)
v1(t)
...
Lowpass
Lowpass
Lowpass
...
Bandpass
Bandpass
Bandpass
To allow for a coexistence of different communication systems and
standards over the entire usable frequency range, the allocation of
frequencies for different purposes is controlled by several national
and international standards and regulation bodies.
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7.4.2 Time-Division Multiplexing
TDM is based on the sampling theorem.
Transmission of oneband-limitedmessage signal engages trans-mission channel for only a fraction of the sampling interval.
Time interval between adjacent samples is cleared for use by
other message signals.
Multiplexing
Lowpass filtering to restrict bandwidth to || M Commutator
Takes narrow samples of each of the Imessage signals atrate1/T > /M
Sequentially interleavesIsamples inside sampling intervalT Pulse modulation
......
LowpassxI(t)
Lowpassx2(t)
Lowpassx1(t)
Commutator
modulatorPulse-
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Demultiplexing
Pulse demodulator produces narrow samples
Decommutator distributes samples
Lowpass filtering to reconstruct message signal
Decommutator
Pulse-demodulator ...
Lowpass
Lowpass
Lowpass v1(t)
v2(t)
vI(t)
...
Timing synchronization between commutator and decommutator
critical
Appropriate choice of pulse shape and pulse demodulation to avoid
intersymbol interference
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