smps lecture 1
TRANSCRIPT
Switch Mode Power Supplies:From Circuit Theory to the Workbench
Michael Tse
Power Electronics Research Centre
Department of Electronic & Information Engineering
Hong Kong Polytechnic University
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Prelude
How much can we trust the theory?
What can we do if the theory doesn’t match the outcome?
Can we live without heuristics?
Are complex models always better?
What makes the engineers lose faith in the theory?
Can theory really be used in practice?
How can we get the most of circuit theory forpractical design and analysis?
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The theorists at fault!!
My EMI filter isn’t quite doing what it is supposed to do. Let
me change the order and a different filter configuration, andtry again.
I need to derive a more accurate model for my power
converter, preferrably up to 10 times the switchingfrequency.
Oh! I have found the answer from my algebra. A duty cycleof 1.2 for this theoretical power factor control!! How could I
achieve this?
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The engineers at fault!!
The snubber gets pretty hot. Let me choose a smaller
resistance.
I would tend to think that the transformer has split
characters. The flyback transformer has never convinced methat it is related to the forward transformer.
Air gap stores more energy.
The output voltage of my constant-power-controlled circuit
isn’t high enough. Let me get a few more turns in thesecondary.
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Objectives
To show how one can arrive at a practical circuit from
consideration of basic circuit theory.
To show how circuit theory can be used to explainphenomena observed in practical circuits.
To show how a switch mode power supply can be
systematically cons-tructed, starting from the simplestconverter topology.
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Contents
Basic topologies and practical requirements
How theory solves problems:
First problem: practical transformer
Second problem: real device switching
Third problem: closed-loop control
Fourth problem: isolation
Fifth problem: input filter
Conclusion
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Genesis of converters Aim: To convert controllable power
from a voltage source to a load,with NO LOSS.
Source Load
?
Lossless
Controllable
Simple
Kirchhoff’s laws restrict terminalconditions.
Source Load
?
Lossless
Controllable
Simple
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An old solution
Lossy linear regulator
Source Load
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Elements wanted
Lossless requirements
current sinking for input
current sourcing foroutput
Ideas
An inductor switchingbetween source and load
Relative sourcing andsinking durations wouldcontrol the energy flow
Bear in mind what
Kirchhoff’s laws say:
Inductors must not be leftopen.
-> An inductor switchingbetween source and load.
-> At least one current pathmust be available at alltimes.
-> At least two switches areneeded to divert theinductor current
-> THREE POSSIBILITIES
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The buck converter
Switch S is turned on and off very quickly, at a rate much
greater than the output filter natural frequency
Control parameter is duty cycle
iLLS
D
ON
OFF
+
–
E
+
–
U
dS t
T
Duration when is on
Period
on= =
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Steady-state operation
Suppose we fix the duty cycle and wait until a steady state is
reached.
Inductor current goes up during the ON time, and goes down duringthe OFF time.
Periodic operation forces
Increment during ON = Decrement during OFF
⇒−
=−
⇒ = ×
( ) ( )E U DT
L
U D T
L
U D E
1
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Putting it to practice
We need transformer isolation
closed-loop control
drivers for MOSFETs
self start-up
snubbers as switching aids
protection
input EMI filter
Proper component selection
mechanical design: heat sink, layout, packaging, etc
Direct
Mandatory
Requirements
Indirect
Mandatory
Requirements
Regulatory
Requirements
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Practical circuit requirement
Forward converter—
transformer isolatedbuck converter
?
Does it work?
?
driver
EMI filter needed
ControlIC andcircuits
?
isolation?
?
start-up
fromaux
output
? ?
EMI
protection (over I / V)
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First problem: practical transformer
The previous forward converter worked only if the
transformer were ideal.
However, practical transformers have magnetisinginductance.
L m
Ideal transformer
1:n
v nv
in
i
2 =
=
1
2 1
1
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What the theory says?
If we have to use a transformer for the forward
converter, the transformer should be idea.
That means INDEFINITELY LARGE magnetizinginductance.
⇓
Either an infinitely permeable core
OR an infinite number of turns
THAT’S IMPOSSIBLE!!
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Probing further into the theory
First, consider the ON time.
Ideal transformer
1:n
Practical transformer
What happens when the FET is off?
Secondary of T/F hasno current.
↓ Primary has no current
either.
↓ Current in magnetising
inductance can gonowhere!!
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Deriving solution: core reset
A path must exist during OFF time to bring the
magnetizing current back to zero
Circuit theory works and explains everything!
Ideal transformer
1:n
Practical transformer
+
–Vz
0A0A
+
– –
+
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Waveforms (with core reset)Secondary current of ideal t/f
same asabove;scaled by factor n
0
0
Primary current of practical t/f
Primary current of ideal t/f
Magntizing current
slopecontrolledby outputinductance
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Requirements for core reset
Negative voltage polarity applied to the winding
during OFF time.
This voltage must be large enough to bring themagnetising current back to zero.
If d = 0.5, then .
If d = 0.8, then .
Technique: clamping the voltage during OFF time.
V Vz in≥
V Vz in≥ 4
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Some core reset possibilities
1:n
Vz
1:n
1:n
1:n
nt
Tertiary winding as voltage clamp
n controls clamped voltage for re-sett
Advantage:
Two-wheeler forward converter
Duty cycle restricted below 0.5
Advantage: simple transformer
Disadvantage:
Disadvantage: bulky transformer
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Recapitulation
Although we cannot make an ideal transformer, we
solve the problem with a reset circuit.
We now care much less how large Lm is, since wehave a way to get around it.
QUESTION: Can the magnetizing inductance be usedto advantage?
YES, in a flyback converter!
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Flyback converter
In this case, we don’t needan ideal transformer. That’sgood. We don’t have itanyway.
The magnetizing inductancebecomes crucial as part ofthe circuit element.
Requirement:
Linear inductor!
Air-gap to augment BHcurve (then more turns toobtain inductance)
1:n
0A0A
1:n
During ON-time, magnetizing inductance charges up.
+
–
reverse polarity, current can't go!
ideal t/f primary current = 0
During OFF-time, magnetizing current forces its way outthrough the ideal t/f primary.
+
–
di/dt negative,hence reversepolarity
+
–
+
–
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Second problem: real switching
Consider turning theswitch in a buckconverter.
The result of this realdevice switching is
POWER LOSS(switching loss)
+
–
E
+
–
U
0
5
idsvds+ –
turn-off
ids
vds
diode won't conduct unless forward biased
ON OFF
diode turns on
ids can't go downunless diode turns on
i.e., vds reaches the input voltage
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Deriving solution: snubber
Give the switch current achance to go down before thediode turns on.
⇓ Set up a PARALLEL CURRENT
PATH right after the turn-offinstant.
⇓ Place a capacitor across the
switch at turn-off to supplycurrent for the output inductor.
+
–
E
+
–
U
0
5
ids
turn-off
idsvds
ON OFF
ids goes down immediately
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Completing the solution
What happens when the switch is turned on again in the next cycle?
The current will rush through the switch!!
⇓ We must protect the switch from such huge in-rush.
The complete snubber is:
Energy loss per cycle
=
+
–
E
+
during turn-on
during turn-off
Snubber
1
2
2C vssnubber
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Other examples (same principle)
+
–
E
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Third problem: closed-loop control
Why?
Because the system is dynamic.
What is a dynamical system?
A simplified definition: a system that does not assume an operating point instantlywhen an input parameter is changed.
0.2
0.4
4.8V
9.6Voutput voltage
duty cycle
Consider a buck converter with input 24V.
Suppose d is forced to step up from 0.2 to 0.4.
Suppose d stays constant, but the load
resistance steps up.
4.8Voutput voltage
load resistance
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The need for control
Obviously we need to controlthe duty cycle if we want thesystem to have a dynamicbehaviour different from thenatural behaviour.
2 common approaches Voltage mode control
Current mode control
+
–
voltage-mode fb
current-mode fb
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Voltage mode control
A general feedback circuit representation is:
Z f
Vref
–+
Vout
–+
Vm
vcon R1
R2
vR R
Z R Rv
R
R R
Z
Z R Rvcon
fref
f
fout
1 2
1 2
2
1 2 1 2
||
( || ) ( || )+
= −
+ +
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Small-signal analysis
We can separate the AC from theDC component.
Let’s not worry about the steady-state operating point.
The small-signal AC equation is:
Taking into account the PWM, wehave
vR R
Z R Rv
R
R R
Z
Z R Rvcon
fref
f
fout
1 2
1 2
2
1 2 1 2
||
( || ) ( || )+
= −
+ +
∆ ∆vZ
Rvcon
fout= −
1
∆ ∆dV
Z
Rv
m
= −1
1
fout
If we know the duty-cycle-to-output small-signal transferfunction, then we can find theloop gain and hence be able todesign the required compensatorto give sufficient bandwidth andstability.
HERE, we need small-signalmodels from circuit theory.
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Design criteria
Fast response — high gain and wide bandwidth of loop gain
Stability — phase shift must be well below 180deg at 0dBcrossover.
The converter is a second-order system which can becomeunstable under closed-loop condition, especially when the gain ishigh causing the phase shift of the loop gain to get close to180deg at 0dB crossover.
We must limit the bandwidth somehow if we allow a high DCgain.
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Workbench construction
The concept of POLE — frequency location where the gain beginsto roll off.
E.g., if the circuit has a capacitor to ground forming an RC networkwith the rest of the equivalent resistance, then a pole exists at1/2 CR Hz.
A simple educated trial-and-error:
Select an RC combination (in the compensation circuit associated withthe control IC) for a deep lag compensation — narrow band first.
Then, relax the time constant (widen the band) until the circuit beginsto oscillate!
Finally, reduce the capacitor value down 10 times to restore stability.
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Current mode control
Essential concept — The systemreduces to first order, more orless!
The system is therefore faster,with less chance for instability.
IDEA:
Make the inductor currentdependent on the output voltageby forcing the current peak tofollow the output voltage analog.
Disqualify the inductor current asa state variable.
The converter becomes firstorder.
Z f
Vref
–+
Vout
–+
v con
R1
R2
currentsensor
R
SQ
driver
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Fourth problem: isolation
Need for isolating the load fromthe mains.
But the control circuit connectsthe two!
Put control in the primary-side
Mainsrectifier
driver
control IC
Vout
+V
aux. supply
bootstrapstart-up
Mainsrectifier
driver
control IC
Vout
+V
aux. supply
Put control in the secondary-side
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Fifth problem: filter
An input filter is always needed toprevent differential-mode andcommon-mode noise from getting intothe mains.
L
N
E
~ differential
commoncommon
SMPS
Basic requirement:
Let 50Hz gets in, butprevent high
frequencies fromgetting out!
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Basic filter theory
Voltage filter (low-passleft-to-right)
Current filter (low-passright-to-left)
Voltage filter (low-passright-to-left)
noise currentat switchingfrequencyand above
50Hz SMPS load
x
noise voltageat switchingfrequencyand above
x+–
Rs
Rs
Rs
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Conceptual placement
Voltage filter (low-passleft-to-right)
Current filter (low-passright-to-left)
Voltage filter (low-passright-to-left)
SMPS
L
N
E
SMPS
L
N
E
Differential-mode filter
Common-mode filter
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Practical placement
NOTE:
The EMI filter often
fails to do what itis supposed to do.
Does the theory
fall short ofanything?
Or have we missed
out someimportant things?!
SMPS
L
N
E
common-modeand differential-mode
capacitor
common-mode chokedifferential-mode choke(may be provided by leakageof common-mode choke)
differential-modecapacitor
differential-modecapacitor
Lc
Ld
Cc1 Cc2Cm1
Cc1
Cm
2+
Cm2,
1 Cc2
Cm
2+ 2
2LdLc+
Ld
2
2Cm1
2Cm2
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Conclusion
The curses to the theory:
A capacitor may not behave as a capacitor.
An inductor may not behave as an inductor.
Parasitics and nonlinearity strike in.
Signals get around the filter, instead of being filtered.
The theory does not fail. The engineers fail to identify the
right ingredients for constructing theories that are viable.
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There is nothing more practical than a good theory.
— James C. Maxwell