non-conventional operation of fets and fet circuits, and ...4 plastic electronics plastic thin-film...
TRANSCRIPT
Non-conventional Operation of FETs and FET Circuits, and Non-
conventional FETsHow much can we gain and what are the
applications
M. Jamal Deen
ECE Department, McMaster UniversityHamilton, Ontario L8S 4K1 Canada
E-mail: [email protected]
2
ITRS Predictionsf
f
Linewidth
RF Frequency
t
Linewidth
Max. RF Frequency from 10 to 100GHz
fT from 45 to 125GHz
fMAX from 90 to 250GHz
Time from 2001 to 2016
tOX from 1.45 to 0.45 nm
Linewidth from 150 to 25 nm
3
Alternate Niche Technology
Finished plastic foil, consisting of a 3 inch polyimide substrate and about 50 integrated circuits.
Each circuit contains a programmable code generator together with a variety of components and test circuits.
http://physicsweb.org/article/world/12/3/11http://researchweb.watson.ibm.com/journal/rd/451/dimitrakopoulos.html
4
Plastic Electronics
Plastic thin-film transistors have a variety of uses, including
wearable electronics,
RFID tags, and
electronic newspapers.
http://www.infineon.com/news/press/211_016e.htm
1000 transistors/IC (Philips 02)plastic chips,electronic barcode or tags, bank or telephone cards, and drivers for flat panel displays
http://www.imo.luc.ac.be/research_activities/oem/plastic_trans.html
5
OutlineWhat can we gain from the 4th MOS terminal
Substrate bias effects and dynamic VTH MOSFETSubthreshold operation of devicesGated-lateral BJTCircuits - oscillator, AGC, mixer
Non-conventional/emerging FET - the PFETApplicationsHow are they madeTypical characteristics
Research issues
Conclusions
6
Why MOSFETs?Dominant technology in information technology systems
Used in almost all digital circuits and systems
Excellent reliability
Large infrastructure of industry; probably most studied device
Performance keeps improving, displacing other technologies
Other flavours of technology are becoming available for higher frequency or future applications- SOI, SOS, SiGe
Highly sophisticated models are available for designers -technology, device, circuit and systems
Offers the best economic and system level integration capabilities of any existing technologies
Is the best solution for system-on-chip (SOC) architectures
7
RF Performance of MOSFETs
DUTs are fabricated in 0.18µm CMOS technology with the channel length 10×6 µm and measured at VDS = 1.0 V.Maximum fT is around 50 GHz and the best NFMIN is about 0.5 dB at 2GHz.
8
MOS Device DetailsImportant Device Details
Source/Drain, Gate and Substrate LDD regionsLOCOS isolation or STIGate oxide thicknessJunction depthSidewall dielectricGate materialChannel dopingContacts of junctions (S and D)Contacts to G (and also B)Types/doping of substrateTechnology: bulk, SOI or SOSTechnology: homo- or hetero-junctionsShort channel effects
gate oxide 4.3nm thickness
gate-sidewall 100nm thickness
in situphosphorus doped polysilicon
Leakage Current
Space Charge Region
Source DrainGateVDD (V)
0 V
0 V
9
Issues in Scaling MOSFETs (IEDM’00, 235)
Issues Reasons (esp. < 100 nm MOS)Short channel effect Reduced L; less reduction in depth & broadness
of junction.
Gate leakage current Direct tunneling through thin oxide
VTH fluctuations Gate length and dopant density fluctuations
Polygate depletion effects Solid solubility limit, increased Evertical and Bpenetration
Junction capacitance Higher doping and abrupt junction
Mobility degradation Increased Nchannel, increased Evertical and Bpenetration
Junction leakage Shallow junctions with silicide metallization
S/D resistance Shallow junctions
Gate sheet resistance Narrow gate width
10
Recent MOS Technologies (IEDM’00, 235)
Elevated S/D. Lower Rparasitic & junction leakage. Better SCEBandgap engineering. SiGe S/D. Improved SCENi silicide. Lower Rparasitic. Improved transistor performance
S/D engineering
Atomic layer doping. Si molecular epitaxyLow energy implantation, optimized annealsPlasma doping. Laser or spike annealing. SiGe extension
Shallow junction
Poly SiGe gate. Reduced polydepletion. Better PMOS.Poly/Metal (Cu,W) stack gate. Reduced gate sheet Res.Dual metal gate - Ti for NMOS and Mo for PMOS
Gate electrode
Oxynitride using NO. Reduced B penetration, VTH spreadOxide scaling evaluation and optimization.
Gate oxide
Channel epitaxy. SCE and Cj improve. Less VTH fluctuationsStrained-Si channel. Enhanced mobility and gM
Halo implant optimization. Reduced SCE, junct. leakage, Cj
Channel engineering
Technology (Below 100 nm CMOS)Process
11
Substrate BiasingImproves the MOSFET performance
Forward substrate biasing (VBS>0) reduces the threshold voltage VT → low voltage applications
Forward substrate biasing (VBS>0) speeds - up the MOSFET → RF applications
Reverse substrate biasing (VBS<0) reduces the drain current ID → low power applications
S
D
BGVDS
VGS VBS
NMOS, 10x0.2µm
VDS=25mV
0.0 0.3 0.6 0.9 1.2
Gate Voltage (V)
10 -12
10 -11
10 -10
10 -9
10 -8
10 -7
10 -6
10 -5
10 -4
10 -3
Dra
in C
urre
nt (A
) 0.5V
-0.5V
0V
12
DTMOS (IEDM’00, 451)
GateDrainSource
Conv. Body
tBox=360nm
DT
tSi=200nm
0
0.1
0.2
0.3
0.4
0.2 0.4 0.6 0.80Body Bias (V)
V TH
(V)
Lpoly=80nm
In pocketB pocket
10µm
Sour
ce
Sour
ce
Drain
Gate/Body
f max
(GH
z)
0.0 0.5 1.0
Rgate (Ω /Sq)
50
100
150
Gate length = 80nm
Finger length = 10µm
1.50.0 0.5 1.00
50
100
150 f T
, fm
ax(G
Hz)
VGS (V)
fT
fmax
DTConv.
Lpoly=80nm, VDS=1VDT
Conv.
Lpoly=80nm
VDS=1V
-0.5 0.0 0.5 1.0 1.510-12
10-10
10-8
10-6
10-4
10-2
0
200
400
600
800
1000
1200
VGATE (V)
I drai
n(A
/µm
)
g M(m
S/m
m)
13
Circuit Description VDD
VBP
VBN
Output buffer
501 stage
Fully integrated Ring VCO Fabricated in 0.18 µm technologyVDD
VoutVin
VBP
VBN
µm1.6=W18.0=L µm
µm8.1=W18.0=L µm
Vin Vout
VDDVBP
VBN
14
Oscillation Frequency
time
VDD
tPHL+ tPHL
VDD
2
V1 V2 V3
CL
V1 V2
VDD
VBP
VBN
V3
CL, the effective loading seen by each inverter, is charged and discharged
Charge and discharge at 3 consecutive Inverters output
D,AVG
L DDo
IN C V
f =• • N = number of stages
fo = frequency of oscillationPHL PLH
o1
N (t t )f =
⋅ +
15
Power ConsumptionCurrent from power supply has two components:
load current ICL,
short circuit current ISC (negligible).
2L DD o NC V fP = • • •
CL
Vin
ICL
VDD
VBP
VBN
ISC
fo×N = constant ==>
Power consumption is independent of the number of stages
2L DD
PHL PLH
C V(t t )
P ⋅=
+
16
Sub-Threshold Operation of MOSFETThe sub-threshold I-V characteristics of a MOSFET
φ φ − = − −
GS DSo
T T
thD
V VI exp 1 exV pn
I
0.15
VDS (V)
Measured
0.15
10-9
10-10
10-11
10-12
10-13
10-14
Calculation
0.20
0.10
0.04V
VGS=-0.01V
0 0.05 0.1 0.15
I D(A
)
TkTq
φ =
Vth = threshold voltage
n = sub-threshold slope
17
Sub-Threshold Operation of InverterVoltage transfer characteristics of inverter operating in sub-threshold is similar to that of strong inversion.
0
0.2
0.4
0.6
0.0 0.2 0.4 0.6 Vin (V)
Vo
ut(V
)
VBS=0
ModelMeas
Analyzing the operation of inverter in sub-threshold
Measurement: functional down to ~ 80 mV supply.
0.0 0.05 0.1 0.15 0.2Vout (V)
1
10
100
1000 Vin=0.15 V
0.125
0.10.0940.075
0.05
NMOSFET
PMOSFET
0.1
Vin=0.05 V
0.0750.094
0.125
0.15
0.0 0.05 0.1 0.15 0.2Vout (V)
1
10
100
1000 Vin=0.15 V
0.125
0.10.0940.075
0.05
NMOSFET
PMOSFET
0.1
Vin=0.05 V
0.0750.094
0.125
0.15
0.0 0.05 0.1 0.15 0.2Vout (V)
1
10
100
1000 Vin=0.15 V
0.125
0.10.0940.075
0.05
NMOSFET
PMOSFET
0.1
V
I DD
(pA
)
18
Experimental ResultsOperation with VDD down to ~80 mV
5 St
age-
VCO
, f
(MH
z)5
Stag
e-VC
O ,
f (M
Hz)
5 St
age-
VCO
, f
(MH
z)5
Stag
e-VC
O ,
f (M
Hz)
0
10
20
30
40
0 0.5 1 1.5 2Supply Voltage, VDD (V)
501
stag
e -VC
O ,
f (M
Hz)
calculationMeasured
VBS=0
0
10
20
30
40
0 0.5 1 1.5 2Supply Voltage, VDD (V)
501
stag
e -VC
O ,
f (M
Hz)
calculationMeasured
VBS=0
0
10
20
30
40
0 0.5 1 1.5 2Supply Voltage, VDD (V)
501
stag
e -VC
O ,
f (M
Hz)
calculationMeasured
VBS=0
0
10
20
30
40
0 0.5 1 1.5 2Supply Voltage, VDD (V)
501
stag
e -VC
O ,
f (M
Hz)
calculationMeasured
VBS=0
0 0.5 1 1.5 2Supply Voltage, VDD (V)
501
stag
e-VC
O ,
f (M
Hz)
CalculationMeasured
10 0
10 +2
10 -2
10 -4
10 -6
10 +4
10 +2
10 0
10 -2
10 -4
VBS=0
0 0.5 1 1.5 2Supply Voltage, VDD (V)
501
stag
e-VC
O ,
f (M
Hz)
CalculationMeasured
10 0
10 +2
10 -2
10 -4
10 -6
10 +4
10 +2
10 0
10 -2
10 -4
VBS=0
0 0.5 1 1.5 2Supply Voltage, VDD (V)
501
stag
e-VC
O ,
f (M
Hz)
CalculationMeasured
10 0
10 +2
10 -2
10 -4
10 -6
10 +4
10 +2
10 0
10 -2
10 -4
VBS=0
0 0.5 1 1.5 2Supply Voltage, VDD (V)
501
stag
e-VC
O ,
f (M
Hz)
CalculationMeasured
10 0
10 +2
10 -2
10 -4
10 -6
10 +4
10 +2
10 0
10 -2
10 -4
VBS=0
For VDD below ~80 mV loop gain < 1, the Barkhausen condition does not hold and circuit stops oscillating
19
Frequency Control MechanismPropagation delays tPHL, tPLH determine oscillation freq.
N.(tPHL+ tPLH
1f o =)
tPHL, tPLH are determined by the rate of charge and discharge of CL through N and PMOSFET:
CL
ICL
VDD
Vin
VBP
charging
Vout
Vin VouttPLH
CL
ICL
Vin
VBN
dischargingVout
Vin VouttPHL
20
Body Bias To Control Frequency Changing the threshold voltage of N and PMOSFET changes the charge and discharge current.
By changing the body voltage of N and PMOSFET, their threshold voltages Vthare changed:
0
0.1
0.2
0.3
0.4
0.2 0.4 0.6 0.80
Body Bias (V)
V TH
(V)
Lpoly=80nm
In pocketB pocket
Vth = Vtho + γ( VFB + VSB − VFB )
21
Body Bias for Frequency ControlVBS and VDD control f from a few tenths of a Hz to 40 MHz (for a 501 stage oscillator).
Measurement results
10-10
10-8
10-6
10-4
10-2
10+2
-2 -1 0 1
Freq
uenc
y, f
(MH
z)
0.6 V
VDD=0.2 V
Model
Meas.
1.8 V
1 V
1.4100
VBS (V)
10-10
10-8
10-6
10-4
10-2
10+2
-2 -1 0 1
Freq
uenc
y, f
(MH
z)
0.6 V
VDD=0.2 V
Model
Meas.
1.8 V
1 V
1.4100
VBS (V)
10-10
10-8
10-6
10-4
10-2
10+2
-2 -1 0 1
Freq
uenc
y, f
(MH
z)
0.6 V
VDD=0.2 V
Model
Meas.
1.8 V
1 V
1.4100
VBS (V)
10-10
10-8
10-6
10-4
10-2
10+2
-2 -1 0 1
Freq
uenc
y, f
(MH
z)
0.6 V
VDD=0.2 V
Model
Meas.
1.8 V
1 V
1.4100
VBS (V)
10-10
10-8
10-6
10-4
10-2
10+2
-2 -1 0 1
Freq
uenc
y, f
(MH
z)
0.6 V
VDD=0.2 V
Model
Meas.
1.8 V
1 V
1.4100
VBS (V)
10-10
10-8
10-6
10-4
10-2
10+2
-2 -1 0 1
Freq
uenc
y, f
(MH
z)
0.6 V
VDD=0.2 V
Model
Meas.
1.8 V
1 V
1.4100
VBS (V)
10-10
10-8
10-6
10-4
10-2
10+2
-2 -1 0 1
Freq
uenc
y, f
(MH
z)
0.6 V
VDD=0.2 V
Model
Meas.
1.8 V
1 V
1.4100
VBS (V)
Body bias controls fthrough Vth which changes IDSAT
22
Tuning RangeThe frequency of the VCO is tuned by body bias voltage in both reverse and forward directions
0
10
20
30
40
0 0.2 0.4 0.6 0.8Forward Body Bias, (V)
Freq
uenc
y, f
(MH
z)
VDD=1.8 V
1.4 V
1 V
0.6 V
0
10
20
30
40
-1 -0.5 0Reverse Body Bias, (V)
Freq
uenc
y, f
(MH
z) VDD=1.8 V
1.4 V
1 V
0
10
20
30
40
0 0.2 0.4 0.6 0.8Forward Body Bias, (V)
Freq
uenc
y, f
(MH
z)
VDD=1.8 V
1.4 V
1 V
0.6 V
0
10
20
30
40
0 0.2 0.4 0.6 0.8Forward Body Bias, (V)
Freq
uenc
y, f
(MH
z)
VDD=1.8 V
1.4 V
1 V
0.6 V
0
10
20
30
40
-1 -0.5 0Reverse Body Bias, (V)
Freq
uenc
y, f
(MH
z) VDD=1.8 V
1.4 V
1 V
0
10
20
30
40
-1 -0.5 0Reverse Body Bias, (V)
Freq
uenc
y, f
(MH
z) VDD=1.8 V
1.4 V
1 V
0
10
20
30
40
0 0.2 0.4 0.6 0.8Forward Body Bias, (V)
Freq
uenc
y, f
(MH
z)
VDD=1.8 V
1.4 V
1 V
0.6 V
0
10
20
30
40
0 0.2 0.4 0.6 0.8Forward Body Bias, (V)
Freq
uenc
y, f
(MH
z)
VDD=1.8 V
1.4 V
1 V
0.6 V
0
10
20
30
40
-1 -0.5 0Reverse Body Bias, (V)
Freq
uenc
y, f
(MH
z) VDD=1.8 V
1.4 V
1 V
0
10
20
30
40
-1 -0.5 0Reverse Body Bias, (V)
Freq
uenc
y, f
(MH
z) VDD=1.8 V
1.4 V
1 V
0
10
20
30
40
0 0.2 0.4 0.6 0.8Forward Body Bias, (V)
Freq
uenc
y, f
(MH
z)
VDD=1.8 V
1.4 V
1 V
0.6 V
0
10
20
30
40
0 0.2 0.4 0.6 0.8Forward Body Bias, (V)
Freq
uenc
y, f
(MH
z)
VDD=1.8 V
1.4 V
1 V
0.6 V
0
10
20
30
40
-1 -0.5 0Reverse Body Bias, (V)
Freq
uenc
y, f
(MH
z) VDD=1.8 V
1.4 V
1 V
0
10
20
30
40
-1 -0.5 0Reverse Body Bias, (V)
Freq
uenc
y, f
(MH
z) VDD=1.8 V
1.4 V
1 V
e.g., for VDD=1.8 V: fo= 6.538 ×VBS + 30.228 MHz
23
Power Consumption - Ring OscillatorPower consumption is from less than a nW to a few mW and is independent of the number of stages
10-12
10-8
10-4
10+2
-2 -1 0 1
ModelVDD=0.2 V
0.6 V
1 V
1.8 V
Meas.
1001.4 V
10-12
10-8
10-4
10+2
-2 -1 0 1Body Bias, VBS (V)
Pow
er, P
(mW
)
ModelVDD=0.2 V
0.6 V
1 V
1.8 V
Meas.
1001.4 V
2L DD o NC V fP = • • •
2L DD
PHL PLH
C V(t t )
P ⋅=
+
24
LTV Phase Noise Model - Ring Osc.An Impulse Sensitivity Function, Γ(ωt) , describes the time
dependence of φ(t) on noise in Ring Oscillators:
time
VddVdd
2
Ring Oscillator Output
Γ(ωοt)
time
tftr
f
r
tAt
=
∫
Ideal integration
φ(t)
Γ(ωοt)
in(t)
Vout
(A is an indication of waveform asymmetry)
According to LTV model, the conversion of noise in(t) to φ(t) is described by the following system:
25
LTV Phase Noise Model - Ring Osc.In LTV model, DC and rms values of Γ(ωt) determine the
conversion of 1/f and white noise into φ(t), respectively
In ring oscillator, Γdc and Γrms can be shown to be
)1()1(12
22 AA
N +−=Γdc
ηπ
333
2
)1(11
382
AA3
Nrms ++=Γ
ηπ
N = number of stages,
η ≈ 0.75 is a fitting constant.
Therefore, by adjusting the waveform symmetry, A~1, (e.g., using MOSFET’s body bias) it is possible to decrease the effect of 1/f and white noise.
26
LTV Phase Noise Model - Ring Osc.Output spectrum of ring VCO has 2 slopes of 1/f3 and 1/f2 with respect to offset frequency fm.
Up-converted 1/f LF noise
Up-converted white noise noisephase
f1
2m
noisephasef1
3m
f1
3m
S Φ(f m
), dB
c/H
z
log fmfc(VCO)
f1
2m
Corner frequency fc is used as a criteria for 1/f noise up-conversion:
πΦ m 2
2rms
2m
2 2L DD
2nΓ
f= •
8 C V
i ∆fS (f )
C(VCO) C(MO
2dc
2r
S)
ms
Γ
Γ= f f
LTV model gives the phase noise due to white noise in/∆f as:2
27
VBS Effect - 1/f Noise Up-ConversionBody bias also changes the Γdcthrough changing the waveform symmetry, which affects the phase noise.
The 1/f noise in a MOSFET:
KF is reduced with forward bias VBS for a fixed VDD (i. e., 1/f noise is reduced).
fIKi
2DF2
f1
×=
-70
reverse ← VBS (V)→ forward
f=1Hz, VDS=0.6V
Weak inversionStrong inversion
, dB
/Hz
S I/ID2
S I/ID2
S I/ID2
S I/ID2
S I/ID2
S I/ID2
S I/ID2
S I/ID2
-75
-80
-85
-900.80.40-0.4-0.8
Slope ~ -8dB/V
A)(1A)(1
N1
η2πΓ
22dc +−=
10
V DD =1.3 V
10
-1.5 -1 -0.5 0 0.5 1VBS (V)
VDD=1.3 V
10
V DD =1.3 V
10
-1.5 -1 -0.5 0 0.5 1VBS (V)
VDD=1.3 V
10
V DD =1.3 V
10
-1.5 -1 -0.5 0 0.5 1VBS (V)
VDD=1.3 V
10
V DD =1.3 V
10
-1.5 -1 -0.5 0 0.5 1VBS (V)
VDD=1.3 V
10
V DD =1.3 V
10
-1.5 -1 -0.5 0 0.5 1VBS (V)
0
20
40
-1.5 -1 -0.5 0 0.5 1VBS (V)
Freq
uenc
y (M
Hz)
0
4.10-12
DC
Val
ue o
f ISF
,Γ
VDD=1.3V
2.10-12
DC
28
Effect of VDD on Phase NoiseLowering VDD decreases IDand therefore 1/f noise is decreased.
Circuit is designed to provide symmetry at VDD=1.8 V; reducing VDD increases Γdc
Effect of ID dominates that of Γdc; lowering VDD decreases the phase noise.f
IKi DF2
f1
×=2
0
20
40
0 0.5 1 1.5 2VDD (V)
0
VBS=0
5×10-12
1×10-11
Γ
0
20
40
0 0.5 1 1.5 2VDD (V)
0
VBS=0
5×10-12
1×10-11
Γ
0
20
40
0 0.5 1 1.5 2VDD (V)
0
VBS=0
5×10-12
1×10-11
Γ
0
20
40
0 0.5 1 1.5 2VDD (V)
0
VBS=0
5×10-12
1×10-11
Γ
S I, d
BA
/Hz
Reverse VBS
~ID2
VDS=0.6V
Reverse VBS
~ID2
VDS=0.6V
Reverse VBS
~ID2
VDS=0.6V
Reverse VBS
~ID2
VDS=0.6V
Reverse VBS
~ID2
~ID2
VDS=0.6V-170
-190
-210
-230
-250
-270
Reverse VBS
~ID2
~ID2
VDS=0.6V
Reverse VBS
~ID2
~ID2
VDS=0.6V
Reverse VBS
~ID2
~ID2
VDS=0.6V
Reverse VBS
~ID2
~ID2
VDS=0.6V
ID (A)
Reverse VBS
~ID2
~ID2
VDS=0.6V
10-10
-170
-190
-210
-230
-250
-27010-8 10-6 10-4
DC
Val
ue o
f ISF
, D
CD
C V
alue
of I
SF,
DC
DC
Val
ue o
f ISF
, D
CD
C V
alue
of I
SF,
DC
29
VBS Dependence of Phase Noise
Generally the phase noise decreases with forward body bias, because 1/f noise in MOSFET is lower.
Also, the waveform symmetry improves.
Modeling agrees well with the measured results.
-100
-90
-80
-70
-60
-50
-2 -1 0 1Body Bias, VBS (V)
Phas
e N
oise
, dB
c/H
z
ModelMeasured
1kHzVDD =1.3 V
10kHz
30
VDD Dependence of Phase NoiseDecrease in VDD decreases the current ID,
Decrease in ID reduces the 1/f noise, which reduces the phase noise,
Decrease in VDD disturbs the waveform symmetry but the overall phase noise decreases due to decrease in ID.
Modeling agrees well with measurement down to VDD=0.5 V.
-140
-120
-100
-80
-60
-40
0 0.5 1 1.5 2Supply Voltage, VDD (V)
Phas
eN
oise
, dB
c/H
z
Model
Measured
VBS=0 V 1kHz
10kHz
Measurement for VDD<0.5 is possible if N < 501.
31
Measured Phase Noise vs. VDD and VBS
-100
-90
-80
-70
-60
-50
1000 10000
Offset Frequency, fm (Hz)
Phas
e N
oise
, dB
c/H
z
to 0.5
Decrease of VDD from 1.8 V
~1/f3
VBS=0
-110
-100
-90
-80
-70
-60
-50
103 104 105
Offset Frequency, fm Hz
+0.6 Forward- 0.6 ReverseZero Bias
1/f3
VDD=1.3 V
-110
-100
-90
-80
-70
-60
-50
103 104 105
Offset Frequency, fm HzPh
ase
Noi
se, d
Bc/
Hz +0.6 Forward
- 0.6 ReverseZero Bias
1/f3
VDD=1.3 V
-110
-100
-90
-80
-70
-60
-50
103 104 105
Offset Frequency, fm Hz
+0.6 Forward- 0.6 ReverseZero Bias
1/f3
VDD=1.3 V
-110
-100
-90
-80
-70
-60
-50
103 104 105
Offset Frequency, fm HzPh
ase
Noi
se, d
Bc/
Hz +0.6 Forward
- 0.6 ReverseZero Bias
1/f3
VDD=1.3 V
Experimental results show the improvement of phase noise with forward body bias and lowering of VDD.
32
Phase Noise - Weak InversionFor VDD ≤ 0.6 V, this circuit can be used:
VoutVin
VDD
-100
-80
-60
-40
-20
0
0 101 102 103 104 105
0.6 V7.8 MHz
0.3 V58 kHz
White noise
1/f2
-100
-80
-60
-40
-20
0
0 101 102 103 104 105
Offset Frequency, fH (Hz)
Phas
e N
oise
, dB
c /H
z
0.6 V7.8 MHz
0.2 V2.6 kHz
White noise
Weak Inversion
1/f2
VDD=VBS
By reducing the number of stages to 3, the frequency increases to above 1 GHz with no increase in phase noise.
For VDD ≤ 0.6V, phase noise is dominated by white noise.
33
Gated Lateral Bipolar Transistor
n-well n+
G
E C
B
p+
p+p+
n- well
p- substrate
n+
plugLPNP
PMOS
G C BE
VPNP
RERC
E C
G
B
34
GLBT-Based Circuits
~VG
VE
vin
VC
RLVout
CLB
C
G
E
E
B
C
G~
VLO
VRF
VIF
10k50
50
50µF
50mH
10µF
10µF
50mH
50µF~
~
VGA
Mixer
0 1500 300 450 600-55
-45
-35
-35
-15
IF, 0.5MHz
IF, 2MHz
PRF = 0dBmPLO = 0 - 14dBmVG = 0VVE = 0.76 - 0.82V
Signal (RF) Frequency
IF O
utpu
t Pow
er (d
Bm)
35
Polymer Field-Effect Transistor - PFET
SiO2
Gate
Source Draindox
Polymer
L L
Insulator
Gate
Source Drain
dox
Polymer
Active Matrix DisplaysElectronic TagsHigh Voltage DriversSensorsImagers - UV, X-Ray
Large Area DeviceLow Power DeviceSelective SensitivitySimple TechnologyLow Cost Fabrication
36
Alternate Niche Technology
Finished plastic foil, consisting of a 3 inch polyimide substrate and about 50 ICs.
Each circuit contains a programmable code generator together with a variety of components and test circuits.
http://physicsweb.org/article/world/12/3/11http://researchweb.watson.ibm.com/journal/rd/451/dimitrakopoulos.html
37
Charge Transport in PolymersCharge transport in molecule is easy
Between molecules is difficult because of disorder
Transport due to charge hopping between localized states in energy and space
Ordering ⇔ ease of hopping
Structure of polymer ⇔ deposition method
Solution processed ⇔ poor ordering
Vacuum deposited ⇔ good ordering
38
PFET’s Electrical Characteristics
0.02 0.04 0.06 0.080Mobility (cm2/Vs)
0
2
4
6
8
10
12
14
Cou
nts
-2.4
-1.6
-0.8
0
I D (µ
A)
-30-20-100V (V)
VGS,V
-30-26
-100
-20
DS
Pentacene PFETs from one waferD. de Leeuw, et. al., IEEE-IEDM, 293-296, 2002.
Pentacene (top contact)
P. Necliudov, et al., Journal of Applied Physics, Vol. 88(9), pp. 5395-5399, 2000.
P3AT (bottom contact)
O. Marinov et al, Proc. FAN, Vol. 5113 pp. 301-312, 2003.
39
Variations of PFET Characteristics
-2.4µA
-1.6 µA
-0.8 µA
0 µA
ID
-30-20-100
VDS, V
VGS,V-30-26-100
-20
Good PolyFET
The shape of the characteristics varies from sample to sample
• ID depends strongly on VGS
• ID is almost independent on VDS• Significant part of IDis independent of VGS
• The bulk conductance prevails over the field effect
-0.6µA
-0.4 µA
-0.2 µA
0 µA
ID
-30-20-100
VGS,V
-30-20-100
VDS, V
Diode-like TFT
-0.12 µA
-0.08 µA
-0.04 µA
0 µA-30-20-100
VDS, V
ID
-30-20-100
VGS,V
Leaking PolyFET
-0.9µA
-0.6 µA
-0.3 µA
0 µA-30-20-100
VDS, V
ID
-30-20-100
VGS,V
Resistive TFT
40
Charge Buildup Increases the Leakage
010
20300
0.2
0.4
0.6
0.8
1
-VDS, V
Measurement
Time
-ID, µ
A
10sec3min
10min30min
100min
Field-effect current decreases with time
10-9
10-8
10-7
10-6
0.1 1 10 100Measurement Time, min
-ID, A
Increasing the
Leakage current increases with time
The charge buildup:
• Increases VT → ID decreases; and
• Modulates the polymer conductivity
SiO2Gate
S DCharge buildup
41
P3AT-Thin Film TransistorsResearch Project: Microelectronic Laboratory at McMaster University in collaboration with SFU
Active material: A continuous film of a semiconducting polymer made by spin coating
polymer
Gate
DrainSource
Insulator: SiO2
Substrate: n+Si
Gate
polymer
Gate
DrainSource
Insulator: SiO 2
Gate
polymer
Gate
DrainSource
Insulator: SiO2
Substrate: n+Si
Gate
polymer
Gate
DrainSource
Insulator: SiO2
Gate
0
1
2
3
-40-30-20-100
VGS=-40 V
-25 V
-30 V
-35 V
P3HDT
I D(µ
A)
VDS (V)
0.0
0.5
1.0
1.5
-40-30-20-100VDS (V)
I D(µ
A)
VGS=-28 V
-12 V-16 V
-20 V
-24 V
0V
P3HT
P3HT=Poly(3-hexylthiophene) P3HDT=Poly(3-hexadekylthiophene)
42
DC vs. Polymer, Annealing & DopingI D
, A
10-10
10-8
10-6
0.00
01%
Ag
(P3H
DT)
0.00
10%
Ag
(P3H
DT)
0.01
00%
Ag
(P3H
DT)
0.10
00%
Ag
(P3H
DT)
1.00
00%
Ag
(P3H
DT)
10.0
000
% A
g (P
3HD
T)
110100100010000100000
Rat
io, a
.u.
IOFF ION
ON/OFF ratio
Polymer
P3H
TP3
OT
P3D
DT
P3H
DT
118o C
(P3H
DT)
140o C
(P3H
DT)
Ann
eale
d @
Doping
No
Ag
(P3H
DT)
Longer polymer chain ⇒ better PFET
Improper high annealing temperature ⇒ worse PFET
Changing the doping ⇒ indifferent
Polymer and its deposition conditions are the most important factors for PFET fabrication and performance characteristics
43
Recommendations for FabricationRecommendations for fabrication of polymer thin film transistorsPolymers with longer chains (e.g. P3DDT or P3HDT) give better electrical performance – High ON-current, Low OFF-current, High ON/OFF ratio;
Polymer deposition is very important. Solutions with lower concentration of polymer should be preferred;
Higher spin coating speed gives higher on/off ratio.
P3HDT
P3OT10-8
10-7
10-6
10-5
-40-30-20-100
VDS (Volt)-I D
(Am
ps)
-32V
VGS
-32V
-22V
-22V
Polymer type is the most important factor
44
Drain Current ID vs. Temperature
before
after heating
VGS = -32V
-24V
-32V
-26V0
1
2
3
-40-30-20-100
-I D(µ
A)
VDS (V)
P3HDT-C16
0
1
2
23 35 45 55 65Temperature (OC)
I D(µ
A)
saturationlinear
Bias: VGS=22.6V
VDS=15V for saturation region
VDS=5V for linear region
The DC performance of the polymer FET (e.g. ID) decreases at temperatures above 40OC.The degradation is not recoverable.
45
Injection Limit in IDLM - Variations
Si O2
Gate
Source Drain
VDS
VGS
dox
d,VBIPolymer
-2.4µA
-1.6 µA
-0.8 µA
0 µA
ID
-30-20-100
VDS, V
VGS,V-30-26-100
-20
Low disorderHigh VBI
-0.6µA
-0.4 µA
-0.2 µA
0 µA
ID
-30-20-100
VGS,V
-30-20-100
VDS, V
-0.12 µA
-0.08 µA
-0.04 µA
0 µA-30-20-100
VDS, V
ID
-30-20-100
VGS,V
High disorderLow VBI
-0.9µA
-0.6 µA
-0.3 µA
0 µA-30-20-100
VDS, V
ID
-30-20-100
VGS,V
Very high disorderVBI=0
Polymer deposition is an important factorHole injection from
source due to VGS
46
Printing TechnologiesCourtesy of John Rogers, Lucent Technologies, now at Univ. Illinois, UC
Adv. Mat. 11(9), p. 741 (1999) (left)
Science 291, p. 1502 (2003) (bottom)
47
UL Area Printed Plastic CircuitsCollaboration between Lucent and DuPont
4096 transistors6ft2 area3 printed levels
Courtesy of John Rogers, Lucent Technologies, now at Univ. Illinois, UC
APL 82, p. 463 (2003)
48
E-Ink DisplaysPaul Drzaic, director of technology for E Ink demonstrates E Ink’s flexible display prototype
Prototypes - 25-square-inch display area made up of several hundred pixels.
Displays were constructed using two ground-breaking developments
Transistors (from Bell labs) in these circuits are made of plastic materials and are fabricated with a low-cost printing process that uses high-resolution rubber stamps. New materials for electronic ink
49
Electronic Paper
Video screen with the properties of paperThe device is fired by plastic transistors that are flexible, inexpensive to make
Transistors work well enough to constantly refresh the screen to create moving pictures.
http://news.nationalgeographic.com/news/2001/12/1206_TVtransistorpaper1.html
50
Operational StabilityPentacene ring oscillator
tested in air without encapsulation
IEDM 2003, Klauk, Infineon
Stage delay is constant and after ~1,000s decreases
Amplitude increases slightly up to ~3,000s and then drops to 0 at ~10,000s
Supply current ~constant at ~1,000, then increases up to ~10,000s, after which circuit fails
10 sec
3,000 sec
6,000 sec
9,000 sec
11,000 sec
51
The Promise of Plastic TransistorsIntegrated circuits made from polymers could usher in a whole new era in computing.Article by Erick Schonfeld, Business Week, Apr 13, 2001
“Back in 1958, when Jack Kilby and Robert Noyce invented the integrated circuit, its transistors were made from metal and silicon.”
“Today's integrated circuits are still forged from the same materials, even though they contain many more millions of transistors.”
“There's a growing scientific movement afoot to build circuits made from entirely new materials. Forget about the rigid metals of old. Now it's all about plastic.”
http://www.business2.com/articles/web/0,1653,11392,00.html
52
Properties of P3HDT
0.0
0.5
1.0
-20-15-10-50VDS, (V)
|I D|,
(µA
)
-32 V
VGS = -36 V
-24 V
-28 V
P3HDT
1000 rpm
Measured
in dark
Good PFET characteristics
Response to visible light
Good photogain at VDS=2V, VGS=0V of 104
Light has same effect as VGS in ID-VDScurves
1.0
0.5
0.0
-20-15-10-50VDS, (V)
|I D|,
(µA
)
Measured under
visible light
0
-12
VGS = -16 V
VGS = +8 V
-8
P3HDT
1000 rpm
10-11
10-9
10-7
10-5
0.1 1 10 100
|I D|,
(µA
) VGS =-35 V
at dark
VGS=0light on
2
1
P3HT3000 rpm
VGS=0in dark
-5
0
5
10
-40 -20 0 20 40VDS, (V)
|I D|,
(µA
)
VGS=-35 Vin dark
VGS= 0 Vlight on
VGS=0in dark
Trap-limit SCLC
Trap-free SCLC
P3HT3000 rpm
VDS, (V)
53
Research Issues - PFETsStability and reliability
Improved electrical performance with inexpensive processing
improved mobilityreduced off current for higher Ion/Ioff ratioreduced bulk leakage currents
Temperature characteristics ↔ degradation
Theoretical description of charge transport
Explore photodetection capabilities of PFETs
Extension of FET-based models now used
54
Research Issues - VB-FETModels for FET with B as fourth active terminal
include all parasitic effects - other transistors, substrate, forward biasing SB, capacitances and resistancesDC and RF - small- and large-signalLF, RF and phase noise behavior
Four terminal FET is newer technologies
SOI, SiGe, BiCMOS flavoursModified CMOS for improved performance
Effects of thin gate oxide and resulting gate currents
tox=1.7nm
n+ n+n-n-
VG
S D
G
p-substrateLDD MOSFET
0.18 µm Tech.
Spacer
oxide
Overlaptunneling current
------------gate tunneling
current
A
A
A
55
Concluding RemarksInteresting opportunities for non-conventional use of existing devices - body biasing in MOSTs
Significant improvement in gM, fT, fmax, noiseCan also create gated lateral BJT - is almost a circuitNew use for existing technologies with superior performance or finer precision
Non-traditional FET technology discussed -polymer FET
Inexpensive, flexible, suitable for niche applicationsCan be combined with OLEDs or E-Ink for displaysMany interesting research issues remain - materials, interface, reliability, stability, theory, modeling
56
AcknowledgementsJ. De La Hidalga (INAOEP, Puebla), Z.X. Yan (Conexant, Newport Beach), D.S. Malhi (Synposis, Toronto), M. Marin (Montpelier) and S. Naseh, O. Marinov, M. Kazemeini (McMaster University) - collaborators and students for body bias, GLBT, Circuits and PFET work
J. Yu, G. Vamvounis, W. Woods and S. Holdcroft (Simon Fraser University, Vancouver) - collaborators and students for PFET work
NSERC of Canada, Micronet and Canada Research Chair -for financial support
57
Muchas Gracias