frequency resposne
TRANSCRIPT
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1. Inverse Z-transform - Partial Fraction
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1. Inverse Z-transform - Partial Fraction
Find the inverse Z-transform of G (z ) =
2z 2 + 2 zz 2 + 2 z 3
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1. Inverse Z-transform - Partial Fraction
Find the inverse Z-transform of G (z ) =
2z 2 + 2 zz 2 + 2 z 3
G (z )z =
2z + 2(z + 3)( z 1)
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1. Inverse Z-transform - Partial Fraction
Find the inverse Z-transform of G (z ) =
2z 2 + 2 zz 2 + 2 z 3
G (z )z =
2z + 2(z + 3)( z 1)
= Az + 3
+ Bz 1
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1. Inverse Z-transform - Partial Fraction
Find the inverse Z-transform of G (z ) =
2z 2 + 2 zz 2 + 2 z 3
G (z )z =
2z + 2(z + 3)( z 1)
= Az + 3
+ Bz 1
Multiply throughout by z + 3 and let z = 3 to get
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1. Inverse Z-transform - Partial Fraction
Find the inverse Z-transform of G (z ) =
2z 2 + 2 zz 2 + 2 z 3
G (z )z =
2z + 2(z + 3)( z 1)
= Az + 3
+ Bz 1
Multiply throughout by z + 3 and let z = 3 to get
A = 2z + 2
z 1 z = 3
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1. Inverse Z-transform - Partial Fraction
Find the inverse Z-transform of G (z ) =
2z 2 + 2 zz 2 + 2 z 3
G (z )z =
2z + 2(z + 3)( z 1)
= Az + 3
+ Bz 1
Multiply throughout by z + 3 and let z = 3 to get
A = 2z + 2
z 1 z = 3=
4
4= 1
Digital Control 1 Kannan M. Moudgalya, Autumn 2007
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2. Inverse Z-transform - Partial Fraction
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2. Inverse Z-transform - Partial Fraction
G (z )z
= Az + 3
+ Bz 1
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2. Inverse Z-transform - Partial Fraction
G (z )z
= Az + 3
+ Bz 1
Multiply throughout by z 1 and let z = 1
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2. Inverse Z-transform - Partial Fraction
G (z )z
= Az + 3
+ Bz 1
Multiply throughout by z 1 and let z = 1 to get
B = 44
= 1
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2. Inverse Z-transform - Partial Fraction
G (z )z
= Az + 3
+ Bz 1
Multiply throughout by z 1 and let z = 1 to get
B = 44
= 1
G (z )z =
1z + 3 +
1z 1 | z | > 3
G (z ) = zz + 3
+ zz 1
| z | > 3
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2. Inverse Z-transform - Partial Fraction
G (z )z
= Az + 3
+ Bz 1
Multiply throughout by z 1 and let z = 1 to get
B = 44
= 1
G (z )z =
1z + 3 +
1z 1 | z | > 3
G (z ) = zz + 3
+ zz 1
| z | > 3
( 3)n
1( n ) + 1( n )Digital Control 2 Kannan M. Moudgalya, Autumn 2007
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3. Partial Fraction - Repeated Poles
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3. Partial Fraction - Repeated Poles
G (z ) = N (z )(z ) pD 1(z )
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3. Partial Fraction - Repeated Poles
G (z ) = N (z )(z ) pD 1(z )
not a root of N (z ) and D 1(z )
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3. Partial Fraction - Repeated Poles
G (z ) = N (z )(z ) pD 1(z )
not a root of N (z ) and D 1(z )
G (z ) = A1z
+ A2(z )2
+ + A p(z ) p
+ G 1(z )
G 1(z ) has poles corresponding to those of D 1(z ) .Multiply by (z ) p
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3. Partial Fraction - Repeated Poles
G (z ) = N (z )(z ) pD 1(z )
not a root of N (z ) and D 1(z )
G (z ) = A1z
+ A2(z )2
+ + A p(z ) p
+ G 1(z )
G 1(z ) has poles corresponding to those of D 1(z ) .Multiply by (z ) p
(z ) pG (z ) = A1(z ) p 1 + A 2(z ) p 2 + + A p 1(z ) + A p + G 1(z )( z ) p
Digital Control 3 Kannan M. Moudgalya, Autumn 2007
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4. Partial Fraction - Repeated Poles
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4. Partial Fraction - Repeated Poles
(z ) pG (z ) = A1(z ) p 1 + A 2(z ) p 2 + + A p 1(z ) + A p + G 1(z )( z ) p
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4. Partial Fraction - Repeated Poles
(z ) pG (z ) = A1(z ) p 1 + A 2(z ) p 2 + + A p 1(z ) + A p + G 1(z )( z ) p
Substituting z = ,
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4. Partial Fraction - Repeated Poles
(z ) pG (z ) = A1(z ) p 1 + A 2(z ) p 2 + + A p 1(z ) + A p + G 1(z )( z ) p
Substituting z = ,
A p = ( z ) pG (z ) | z =
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4. Partial Fraction - Repeated Poles
(z ) pG (z ) = A1(z ) p 1 + A 2(z ) p 2 + + A p 1(z ) + A p + G 1(z )( z ) p
Substituting z = ,
A p = ( z ) pG (z ) | z =
Differentiate and let z = :
l d l
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4. Partial Fraction - Repeated Poles
(z ) pG (z ) = A1(z ) p 1 + A 2(z ) p 2 + + A p 1(z ) + A p + G 1(z )( z ) p
Substituting z = ,
A p = ( z ) pG (z ) | z =
Differentiate and let z = :
A p 1 = ddz (z ) pG (z ) | z =
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4 P ti l F ti R t d P l
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4. Partial Fraction - Repeated Poles
(z ) pG (z ) = A1(z ) p 1 + A 2(z ) p 2 + + A p 1(z ) + A p + G 1(z )( z ) p
Substituting z = ,
A p = ( z ) pG (z ) | z =
Differentiate and let z = :
A p 1 = ddz (z ) pG (z ) | z =
Continuing, A1 = 1
( p 1)!d p 1
dz p 1(z ) pG (z ) | z =
Digital Control 4 Kannan M. Moudgalya, Autumn 2007
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5 Repeated Poles an Example
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5. Repeated Poles - an Example
G (z ) = 11z 2 15z + 6(z 2)( z 1) 2 =
5 Repeated Poles an Example
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5. Repeated Poles - an Example
G (z ) = 11z 2 15z + 6(z 2)( z 1) 2 =
A1
z 1 + A
2(z 1) 2 +
Bz 2
5 Repeated Poles an Example
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5. Repeated Poles - an Example
G (z ) = 11z 2 15z + 6(z 2)( z 1) 2 =
A1
z 1 + A
2(z 1) 2 +
Bz 2
(z 2) ,
5 Repeated Poles an Example
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5. Repeated Poles - an Example
G (z ) = 11z 2 15z + 6(z 2)( z 1) 2 =
A1
z 1 + A
2(z 1) 2 +
Bz 2
(z 2) , let z = 2 , to get B = 20 .
5 Repeated Poles - an Example
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5. Repeated Poles - an Example
G (z ) = 11z 2 15z + 6(z 2)( z 1) 2 =
A1z 1 +
A2(z 1) 2 +
Bz 2
(z 2) , let z = 2 , to get B = 20 . (z 1) 2,
5 Repeated Poles - an Example
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5. Repeated Poles an Example
G (z ) = 11z 2 15z + 6(z 2)( z 1) 2 =
A1z 1 +
A2(z 1) 2 +
Bz 2
(z 2) , let z = 2 , to get B = 20 . (z 1) 2,
11 z2
15z + 6z 2 = A1(z 1) + A 2 + B (z 1)2
z 2
5 Repeated Poles - an Example
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5. Repeated Poles an Example
G (z ) = 11z 2 15z + 6(z 2)( z 1) 2 =
A1z 1 +
A2(z 1) 2 +
Bz 2
(z 2) , let z = 2 , to get B = 20 . (z 1) 2,
11 z2
15z + 6z 2 = A1(z 1) + A 2 + B (z 1)2
z 2With z = 1 , get A2 = 2.
5. Repeated Poles - an Example
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5. Repeated Poles an Example
G (z ) = 11z 2 15z + 6(z 2)( z 1) 2 =
A1z 1 +
A2(z 1) 2 +
Bz 2
(z 2) , let z = 2 , to get B = 20 . (z 1) 2,
11 z2
15z + 6z 2 = A1(z 1) + A 2 + B (z 1)2
z 2With z = 1 , get A2 = 2.Differentiating with respect to z and with z = 1 ,
5. Repeated Poles - an Example
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5. Repeated Poles an Example
G (z ) = 11z 2 15z + 6(z 2)( z 1) 2 =
A1z 1 +
A2(z 1) 2 +
Bz 2
(z 2) , let z = 2 , to get B = 20 . (z 1) 2,
11 z2
15z + 6z 2 = A1(z 1) + A 2 + B (z 1)2
z 2With z = 1 , get A2 = 2.Differentiating with respect to z and with z = 1 ,
A 1 =
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5. Repeated Poles - an Example
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p p
G (z ) = 11z 2 15z + 6(z 2)( z 1) 2 =
A1z 1 +
A2(z 1) 2 +
Bz 2
(z 2) , let z = 2 , to get B = 20 . (z 1) 2,
11z 2
15z
+ 6z 2 = A1(z 1) + A 2 + B (z
1)2
z 2With z = 1 , get A2 = 2.Differentiating with respect to z and with z = 1 ,
A 1 = (z 2)(22 z 15) (11 z 2 15z + 6)
(z 2) 2 z =1= 9
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6. Important Result from Differentiation
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p
6. Important Result from Differentiation
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Problem 4.9 in Text:
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6. Important Result from Differentiation
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Problem 4.9 in Text: Consider
1( n )a n zz a
=
n =0
a n z n , az 1 < 1
Differentiating with respect to a ,
6. Important Result from Differentiation
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Problem 4.9 in Text: Consider
1( n )a n zz a
=
n =0
a n z n , az 1 < 1
Differentiating with respect to a ,
z(z a )2
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6. Important Result from Differentiation
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Problem 4.9 in Text: Consider
1( n )a n zz a
=
n =0
a n z n , az 1 < 1
Differentiating with respect to a ,
z(z a )2
=
n =0
na n 1z n , na n 11( n ) z
(z a )2
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6. Important Result from Differentiation
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Problem 4.9 in Text: Consider
1( n )a n zz a
=
n =0
a n z n , az 1 < 1
Differentiating with respect to a ,
z(z a )2
=
n =0
na n 1z n , na n 11( n ) z
(z a )2
Substituting a = 1 , can obtain the Z-transform of n :
n 1( n ) z
(z 1) 2
6. Important Result from Differentiation
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Problem 4.9 in Text: Consider
1( n )a n zz a
=
n =0
a n z n , az 1 < 1
Differentiating with respect to a ,
z(z a )2
=
n =0
na n 1z n , na n 11( n ) z
(z a )2
Substituting a = 1 , can obtain the Z-transform of n :
n 1( n ) z
(z 1) 2
Through further differentiation,
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7. Repeated Poles - an Example
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7. Repeated Poles - an Example
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G (z ) = 9z 1
2(z 1) 2
+ 20z 2
7. Repeated Poles - an Example
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G (z ) = 9z 1
2(z 1) 2
+ 20z 2
zG (z ) = 9z
z 1
2z
(z 1) 2 +
20z
z 2
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G (z ) = 9z 1
2(z 1) 2
+ 20z 2
zG (z ) = 9z
z 1
2z
(z 1) 2 +
20z
z 2 ( 9 2n + 20 2n )1( n )
7. Repeated Poles - an Example
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G (z ) = 9z 1
2(z 1) 2
+ 20z 2
zG (z ) = 9z
z 1
2z
(z 1) 2 +
20z
z 2 ( 9 2n + 20 2n )1( n )
Use shifting theorem:G (z )
7. Repeated Poles - an Example
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G (z ) = 9z 1
2(z 1) 2
+ 20z 2
zG (z ) = 9z
z 1
2z
(z 1) 2 +
20z
z 2 ( 9 2n + 20 2n )1( n )
Use shifting theorem:G (z ) ( 9 2( n 1) + 20 2n 1)1( n 1)
Digital Control 7 Kannan M. Moudgalya, Autumn 2007
8. Properties of Cont. Time Sinusoidal Signals
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8. Properties of Cont. Time Sinusoidal Signals
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u a ( t ) = A cos ( t + )
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8. Properties of Cont. Time Sinusoidal Signals
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u a ( t ) = A cos ( t + )u a ( t ) = A cos (2 F t + ) , < t <
A : amplitude
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8. Properties of Cont. Time Sinusoidal Signals
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u a ( t ) = A cos ( t + )u a ( t ) = A cos (2 F t + ) , < t <
A : amplitude: frequency in rad/s : phase in rad
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8. Properties of Cont. Time Sinusoidal Signals
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u a ( t ) = A cos ( t + )u a ( t ) = A cos (2 F t + ) , < t <
A : amplitude: frequency in rad/s : phase in radF : frequency in cycles/s or Hertz
= 2 F
T p = 1F
Digital Control 8 Kannan M. Moudgalya, Autumn 2007
9. Properties of Cont. Time Sinusoidal Signals
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9. Properties of Cont. Time Sinusoidal Signals
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u a ( t ) = A cos ( t + )
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9. Properties of Cont. Time Sinusoidal Signals
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u a ( t ) = A cos ( t + )u a ( t ) = A cos (2 F t + ) , < t <
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9. Properties of Cont. Time Sinusoidal Signals
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u a ( t ) = A cos ( t + )u a ( t ) = A cos (2 F t + ) , < t <
With F xed, periodic with period T p
u a [t + T p]
9. Properties of Cont. Time Sinusoidal Signals
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u a ( t ) = A cos ( t + )u a ( t ) = A cos (2 F t + ) , < t <
With F xed, periodic with period T p
u a [t + T p] = A cos (2 F ( t + 1F
) + )
9. Properties of Cont. Time Sinusoidal Signals
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u a ( t ) = A cos ( t + )u a ( t ) = A cos (2 F t + ) , < t <
With F xed, periodic with period T p
u a [t + T p] = A cos (2 F ( t + 1F
) + )
= A cos (2 + 2 F t + )
9. Properties of Cont. Time Sinusoidal Signals
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u a ( t ) = A cos ( t + )u a ( t ) = A cos (2 F t + ) , < t <
With F xed, periodic with period T p
u a [t + T p] = A cos (2 F ( t + 1F
) + )
= A cos (2 + 2 F t + )= A cos (2 F t + )
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10. Properties of Cont. Time Sinusoidal Signals
Cont signals with different frequencies are different
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Cont. signals with different frequencies are different
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10. Properties of Cont. Time Sinusoidal Signals
Cont signals with different frequencies are different
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Cont. signals with different frequencies are different
u 1 = cos 2 t8, u 2 = cos 2 7t8
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10. Properties of Cont. Time Sinusoidal Signals
Cont signals with different frequencies are different
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Cont. signals with different frequencies are different
u 1 = cos 2 t8, u 2 = cos 2 7t8
0 0.5 1 1.5 2 2.5 3 3.5 41
0.8
0.6
0.4
0.2
0
0.2
0.4
0.6
0.8
1
t
c o s w t
Different wave forms for different frequencies.
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11. Discrete Time Sinusoidal Signals
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11. Discrete Time Sinusoidal Signals
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u (n ) = A cos ( wn + ) , < n < w = 2 f
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11. Discrete Time Sinusoidal Signals
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u (n ) = A cos ( wn + ) , < n < w = 2 f
n integer variable, sample numberA amplitude of the sinusoid
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12. Discrete Time Sinusoids - Identical Signals
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12. Discrete Time Sinusoids - Identical Signals
Discrete time sinusoids whose frequencies are sepa-
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rated by integer multiple of 2 are identical, i.e.,cos (( w0 + 2 )n + ) = cos ( w0n + ) , n
12. Discrete Time Sinusoids - Identical Signals
Discrete time sinusoids whose frequencies are sepa-
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rated by integer multiple of 2 are identical, i.e.,cos (( w0 + 2 )n + ) = cos ( w0n + ) , n All sinusoidal sequences of the form,
12. Discrete Time Sinusoids - Identical Signals
Discrete time sinusoids whose frequencies are sepa-
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rated by integer multiple of 2 are identical, i.e.,cos (( w0 + 2 )n + ) = cos ( w0n + ) , n All sinusoidal sequences of the form,
u k (n ) = A cos( wk n + ) ,
12. Discrete Time Sinusoids - Identical Signals
Discrete time sinusoids whose frequencies are sepa-
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rated by integer multiple of 2 are identical, i.e.,cos (( w0 + 2 )n + ) = cos ( w0n + ) , n All sinusoidal sequences of the form,
u k (n ) = A cos( wk n + ) ,wk = w0 + 2 k ,
12. Discrete Time Sinusoids - Identical Signals
Discrete time sinusoids whose frequencies are sepa-
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rated by integer multiple of 2 are identical, i.e.,cos (( w0 + 2 )n + ) = cos ( w0n + ) , n All sinusoidal sequences of the form,
u k (n ) = A cos( wk n + ) ,wk = w0 + 2 k , < w 0 < ,
12. Discrete Time Sinusoids - Identical Signals
Discrete time sinusoids whose frequencies are sepa-
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rated by integer multiple of 2 are identical, i.e.,cos (( w0 + 2 )n + ) = cos ( w0n + ) , n All sinusoidal sequences of the form,
u k (n ) = A cos( wk n + ) ,wk = w0 + 2 k , < w 0 < ,are indistinguishable or identical.
12. Discrete Time Sinusoids - Identical Signals
Discrete time sinusoids whose frequencies are sepa-
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rated by integer multiple of 2 are identical, i.e.,cos (( w0 + 2 )n + ) = cos ( w0n + ) , n All sinusoidal sequences of the form,
u k (n ) = A cos( wk n + ) ,wk = w0 + 2 k , < w 0 < ,are indistinguishable or identical.
Only sinusoids in < w 0 < are different
12. Discrete Time Sinusoids - Identical Signals
Discrete time sinusoids whose frequencies are sepa-
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rated by integer multiple of 2 are identical, i.e.,cos (( w0 + 2 )n + ) = cos ( w0n + ) , n All sinusoidal sequences of the form,
u k (n ) = A cos( wk n + ) ,wk = w0 + 2 k , < w 0 < ,are indistinguishable or identical.
Only sinusoids in < w 0 < are different
< w 0 < or 12
< f 0 < 12
Digital Control 12 Kannan M. Moudgalya, Autumn 2007
13. Sampling a Cont. Time Signal - Preliminaries
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13. Sampling a Cont. Time Signal - Preliminaries
Let analog signal u a [t ] have a frequency of F Hz
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13. Sampling a Cont. Time Signal - Preliminaries
Let analog signal u a [t ] have a frequency of F Hz
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u a [t ] = A cos(2 F t + )Uniform sampling rate (T s s) or frequency (F s Hz)
t = nT s = n
F s
13. Sampling a Cont. Time Signal - Preliminaries
Let analog signal u a [t ] have a frequency of F Hz
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u a [t ] = A cos(2 F t + )Uniform sampling rate (T s s) or frequency (F s Hz)
t = nT s = n
F su (n ) = u a [nT s ] < n <
13. Sampling a Cont. Time Signal - Preliminaries
Let analog signal u a [t ] have a frequency of F Hz
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u a [t ] = A cos(2 F t + )Uniform sampling rate (T s s) or frequency (F s Hz)
t = nT s = n
F su (n ) = u a [nT s ] < n <
= A cos (2 F T s n + )
13. Sampling a Cont. Time Signal - Preliminaries
Let analog signal u a [t ] have a frequency of F Hz
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u a [t ] = A cos(2 F t + )Uniform sampling rate (T s s) or frequency (F s Hz)
t = nT s = n
F su (n ) = u a [nT s ] < n <
= A cos (2 F T s n + )
= A cos 2 F F s
n +
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14. Sampling a Cont. Time Signal - Preliminaries
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14. Sampling a Cont. Time Signal - Preliminaries
In our standard notation,
-
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u (n ) = A cos (2 fn + )It follows that
f = F
F sw =
F s= T s
14. Sampling a Cont. Time Signal - Preliminaries
In our standard notation,
-
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u (n ) = A cos (2 fn + )It follows that
f = F
F sw =
F s= T s
Reason to callf normalized frequency, cycles/sample.
14. Sampling a Cont. Time Signal - Preliminaries
In our standard notation,
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u (n ) = A cos (2 fn + )It follows that
f = F
F sw =
F s= T s
Reason to callf normalized frequency, cycles/sample.Apply the uniqueness condition for sampled signals
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14. Sampling a Cont. Time Signal - Preliminaries
In our standard notation,
( ) ( f )
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u (n ) = A cos (2 fn + )It follows that
f = F
F sw =
F s= T s
Reason to callf normalized frequency, cycles/sample.Apply the uniqueness condition for sampled signals
12 < f ?
w1 = w0
15. Properties of Discrete Time Sinusoids - Alias
As w0 , freq. of oscillation, reaches maximum
at w0
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at w0 = What if w0 > ?
w1 = w0w2 = 2 w0
15. Properties of Discrete Time Sinusoids - Alias
As w0 , freq. of oscillation, reaches maximum
at w0 =
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at w0 = What if w0 > ?
w1 = w0w2 = 2 w0u 1(n ) = A cos w1n
15. Properties of Discrete Time Sinusoids - Alias
As w0 , freq. of oscillation, reaches maximum
at w0 =
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at w0 = What if w0 > ?
w1 = w0w2 = 2 w0u 1(n ) = A cos w1n = A cos w0n
15. Properties of Discrete Time Sinusoids - Alias
As w0 , freq. of oscillation, reaches maximum
at w0 =
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at w0 = What if w0 > ?
w1 = w0w2 = 2 w0u 1(n ) = A cos w1n = A cos w0n
u 2(n ) = A cos w2n
15. Properties of Discrete Time Sinusoids - Alias
As w0 , freq. of oscillation, reaches maximum
at w0 =
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at w0 = What if w0 > ?
w1 = w0w2 = 2 w0u 1(n ) = A cos w1n = A cos w0n
u 2(n ) = A cos w2n = A cos(2 w0)n
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16. Properties of Discrete Time Sinusoids - Alias
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16. Properties of Discrete Time Sinusoids - Alias
u 1[t ] = cos (2 t8
) ,
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16. Properties of Discrete Time Sinusoids - Alias
u 1[t ] = cos (2 t8
) , u 2[t ] = cos (2 7t8
) ,
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16. Properties of Discrete Time Sinusoids - Alias
u 1[t ] = cos (2 t8
) , u 2[t ] = cos (2 7t8
) , T s = 1
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16. Properties of Discrete Time Sinusoids - Alias
u 1[t ] = cos (2 t8
) , u 2[t ] = cos (2 7t8
) , T s = 1
u 2(n ) = cos (2 7n )
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u 2(n ) cos (2 8)
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16. Properties of Discrete Time Sinusoids - Alias
u 1[t ] = cos (2 t8
) , u 2[t ] = cos (2 7t8
) , T s = 1
u 2(n ) = cos (2 7n8) = cos 2 (1 1
8)n
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2( ) ( 8) (
8)
= cos (2 28
)n = cos (2n
8) = u 1(n )
16. Properties of Discrete Time Sinusoids - Alias
u 1[t ] = cos (2 t8
) , u 2[t ] = cos (2 7t8
) , T s = 1
u 2(n ) = cos (2 7n8) = cos 2 (1 1
8)n
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( ) (8
) (8
)
= cos (2 28
)n = cos (2n
8) = u 1(n )
0 0.5 1 1.5 2 2.5 3 3.5 41
0.8
0.6
0.4
0.2
0
0.2
0.4
0.6
0.8
1
t
c o s w t
Digital Control 16 Kannan M. Moudgalya, Autumn 2007
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17. Fourier Transform of Aperiodic Signals
X (F ) =
x ( t )e j 2F t
dt
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( ) ( )x ( t ) =
X (F )e j 2F t dF
If we let radian frequency = 2 F
x ( t ) = 12
X []e j t d,
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18. Frequency Response
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18. Frequency Response
Apply u (n ) = e jwn to g(n ) and obtain output y:
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18. Frequency Response
Apply u (n ) = e jwn to g(n ) and obtain output y:
y (n ) = g(n ) u (n ) =
k= g(k )u (n k )
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=
k=
g(k )e jw (n k )
18. Frequency Response
Apply u (n ) = e jwn to g(n ) and obtain output y:
y (n ) = g(n ) u (n ) =
k= g(k )u (n k )
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=
k=
g(k )e jw (n k ) = e jwn
k=
g(k )e jwk
18. Frequency Response
Apply u (n ) = e jwn to g(n ) and obtain output y:
y (n ) = g(n ) u (n ) =
k= g(k )u (n k )
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=
k=
g(k )e jw (n k ) = e jwn
k=
g(k )e jwk
Dene Discrete Time Fourier Transform
18. Frequency Response
Apply u (n ) = e jwn to g(n ) and obtain output y:
y (n ) = g(n ) u (n ) =
k= g(k )u (n k )
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=
k=
g(k )e jw (n k ) = e jwn
k=
g(k )e jwk
Dene Discrete Time Fourier Transform
G (e jw ) =
k=
g(k )e jwk
18. Frequency Response
Apply u (n ) = e jwn to g(n ) and obtain output y:
y (n ) = g(n ) u (n ) =
k= g(k )u (n k )
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=
k=
g(k )e jw (n k ) = e jwn
k=
g(k )e jwk
Dene Discrete Time Fourier Transform
G (e jw ) =
k=
g(k )e jwk =
k=
g(k )z k
z = e jw
18. Frequency Response
Apply u (n ) = e jwn to g(n ) and obtain output y:
y (n ) = g(n ) u (n ) =
k= g(k )u (n k )
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=
k=
g(k )e jw (n k ) = e jwn
k=
g(k )e jwk
Dene Discrete Time Fourier Transform
G (e jw ) =
k=
g(k )e jwk =
k=
g(k )z k
z = e jw
= G (z ) | z = e jw
18. Frequency Response
Apply u (n ) = e jwn to g(n ) and obtain output y:
y (n ) = g(n ) u (n ) =
k= g(k )u (n k )
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=
k=
g(k )e jw (n k ) = e jwn
k=
g(k )e jwk
Dene Discrete Time Fourier Transform
G (e jw ) =
k=
g(k )e jwk =
k=
g(k )z k
z = e jw
= G (z ) | z = e jw
Provided the sequence converges absolutelyDigital Control 18 Kannan M. Moudgalya, Autumn 2007
19. Frequency Response
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19. Frequency Response
y (n ) = e jwn
k= g(k )e jwk
= e jwn
G (e jw
)
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19. Frequency Response
y (n ) = e jwn
k= g(k )e jwk
= e jwn
G (e jw
)
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Write in polar coordinates: G (e jw ) = |G (e jw ) | e j - isphase angle:
y (n ) = e jwn |G (e jw ) | e j
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19. Frequency Response
y (n ) = e jwn
k= g(k )e jwk
= e jwn
G (e jw
)
j j j
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Write in polar coordinates: G (e jw ) = |G (e jw ) | e j - isphase angle:
y (n ) = e jwn |G (e jw ) | e j = |G (e jwn ) | e j (wn + )
1. Input is sinusoid output also is a sinusoid with followingproperties:
19. Frequency Response
y (n ) = e jwn
k= g(k )e jwk
= e jwn
G (e jw
)
j j j
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Write in polar coordinates: G (e jw ) = |G (e jw ) | e j - isphase angle:
y (n ) = e jwn |G (e jw ) | e j = |G (e jwn ) | e j (wn + )
1. Input is sinusoid output also is a sinusoid with followingproperties:
Output amplitude gets multiplied by the magnitude of G (e jw )
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2. At where |G (e jw
) | is large, the sinusoid gets amplied
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2. At where |G (e jw
) | is large, the sinusoid gets ampliedand at where it is small, the sinusoid gets attenuated.
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2. At where |G (e jw
) | is large, the sinusoid gets ampliedand at where it is small, the sinusoid gets attenuated. The system with large gains at low frequencies and small
gains at high frequencies are called low pass lters
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2. At where |G (e jw
) | is large, the sinusoid gets ampliedand at where it is small, the sinusoid gets attenuated. The system with large gains at low frequencies and small
gains at high frequencies are called low pass lters Similarly high pass lters
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Digital Control 20 Kannan M. Moudgalya, Autumn 2007
20. Discrete Fourier Transform
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20. Discrete Fourier TransformDene Discrete Time Fourier Transform
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20. Discrete Fourier TransformDene Discrete Time Fourier Transform
G (e jw
)
=
k= g(k )e
jwk=
k= g(k )z
k
z = e jw
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20. Discrete Fourier TransformDene Discrete Time Fourier Transform
G (e jw
)
=
k= g(k )e
jwk=
k= g(k )z
k
z = e jw
= G (z ) | jw
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G (z ) | z = e jw
20. Discrete Fourier Transform
Dene Discrete Time Fourier Transform
G (e jw
)
=
k= g(k )e
jwk
=
k= g(k )z
k
z = e jw
= G (z ) | jw
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G (z ) | z = e jw
Provided, absolute convergence
k=
| g(k )e jwk | <
20. Discrete Fourier Transform
Dene Discrete Time Fourier Transform
G (e jw
)
=
k= g(k )e
jwk
=
k= g(k )z
k
z = e jw
= G (z ) | z = e jw
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G (z ) | z = e jw
Provided, absolute convergence
k=
| g(k )e jwk | <
k=
| g(k ) | <
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20. Discrete Fourier Transform
Dene Discrete Time Fourier Transform
G (e jw
)
=
k= g(k )e
jwk
=
k= g(k )z
k
z = e jw
= G (z ) | z = e jw
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( ) | z = e j
Provided, absolute convergence
k=
| g(k )e jwk | <
k=
| g(k ) | <
For causal systems, BIBO stability.
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21. FT of Discrete Time Aperiodic Signals - De-nition
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21. FT of Discrete Time Aperiodic Signals - De-nition
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21. FT of Discrete Time Aperiodic Signals - De-nition
U (e j ) =
n =
u (n )e jn
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21. FT of Discrete Time Aperiodic Signals - De-nition
U (e j ) =
n =
u (n )e jn
1
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u (m ) = 1
2
U (e j )e jm d
21. FT of Discrete Time Aperiodic Signals - De-nition
U (e j ) =
n =
u (n )e jn
1
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u (m ) = 1
2
U (e j )e jm d
= 1/ 2
1/ 2U ( f )e j 2f m df
Digital Control 22 Kannan M. Moudgalya, Autumn 2007
22. FT of a Moving Average Filter - Example
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22. FT of a Moving Average Filter - Example
y (n ) = 1
3[u (n + 1) + u (n ) + u (n 1)]
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22. FT of a Moving Average Filter - Example
y (n ) = 1
3[u (n + 1) + u (n ) + u (n 1)]
y (n ) =
k=
g(k )u (n k )
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= g( 1) u (n + 1) + g(0) u (n )
22. FT of a Moving Average Filter - Example
y (n ) = 1
3[u (n + 1) + u (n ) + u (n 1)]
y (n ) =
k=
g(k )u (n k )
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= g( 1) u (n + 1) + g(0) u (n ) + g(1) u (n 1)
22. FT of a Moving Average Filter - Example
y (n ) = 1
3[u (n + 1) + u (n ) + u (n 1)]
y (n ) =
k=
g(k )u (n k )
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= g( 1) u (n + 1) + g(0) u (n ) + g(1) u (n 1)
g( 1) = g(0) = g(1) = 13
22. FT of a Moving Average Filter - Example
y (n ) = 1
3[u (n + 1) + u (n ) + u (n 1)]
y (n ) =
k=
g(k )u (n k )
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= g( 1) u (n + 1) + g(0) u (n ) + g(1) u (n 1)
g( 1) = g(0) = g(1) = 13
G e jw =
n =
g(n )z n | z = e jw
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22. FT of a Moving Average Filter - Example
y (n ) = 1
3[u (n + 1) + u (n ) + u (n 1)]
y (n ) =
k=
g(k )u (n k )
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= g( 1) u (n + 1) + g(0) u (n ) + g(1) u (n 1)
g( 1) = g(0) = g(1) = 13
G e jw =
n =
g(n )z n | z = e jw
= 13
e jw + 1 + e jw = 13
(1 + 2 cos w )
Digital Control 23 Kannan M. Moudgalya, Autumn 2007
23. FT of a Moving Average Filter - Example
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23. FT of a Moving Average Filter - Example
G e j = 13
(1 + 2 cos w )
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23. FT of a Moving Average Filter - Example
G e j = 13
(1 + 2 cos w ) , |G e jw | = |13
(1 + 2 cos w ) |
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23. FT of a Moving Average Filter - Example
G e j = 13
(1 + 2 cos w ) , |G e jw | = |13
(1 + 2 cos w ) |
Arg (G ) =0 0 w < 2
3 23 w <
1 / / U p d a t e d ( 1 8 7 0 7 )
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2 / / 5 . 3
3
4 w = 0 : 0 .0 1 : %pi ;5 subplot (2 , 1 , 1 ) ;6 plot2d1 ( g l l ,w,abs (1+2 cos (w) ) / 3 , s t y l e = 2 ) ;7 l a b e l ( ,4 , , Magni tude , 4 ) ;8 subplot (2 , 1 , 2 ) ;9 plot2d1 ( g ln ,w,phasemag (1+2 cos (w) ) , s t y l e = 2 , r e c t =[0
10 l a b e l ( ,4 , w , Phase ,4)Digital Control 24 Kannan M. Moudgalya, Autumn 2007
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24. FT of a Moving Average Filter - Example
|G e jw | = |13
(1 + 2 cos w ) |
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24. FT of a Moving Average Filter - Example
|G e jw | = |13
(1 + 2 cos w ) | ,
Arg (G ) =0 0 w < 2
3 23 w <
101
100
e
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102
101
100
101
103
102
10
a g n u
102
101
100
101
0
50
100
150
200
w
P h a s e
Digital Control 25 Kannan M. Moudgalya, Autumn 2007
25. Additional Properties of Fourier Transform
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25. Additional Properties of Fourier Transform
Symmetry of real and imaginary parts for real valued sequences
G e jw =
n =
g(n )e jwn
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25. Additional Properties of Fourier Transform
Symmetry of real and imaginary parts for real valued sequences
G e jw =
n =
g(n )e jwn
=
n =
g(n ) cos wn j
n =
g(n )sin wn
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25. Additional Properties of Fourier Transform
Symmetry of real and imaginary parts for real valued sequences
G e jw =
n =
g(n )e jwn
=
n =
g(n ) cos wn j
n =
g(n )sin wn
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G e jw =
n =
g(n )e jwn
=
n =
g(n ) cos wn + j
n =
g(n ) sin wn
Re G e jw = Re G e jw
25. Additional Properties of Fourier Transform
Symmetry of real and imaginary parts for real valued sequences
G e jw =
n =
g(n )e jwn
=
n =
g(n ) cos wn j
n =
g(n )sin wn
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G e jw =
n =
g(n )e jwn
=
n =
g(n ) cos wn + j
n =
g(n ) sin wn
Re G e jw = Re G e jw
Im G e jw = Im G e jwDigital Control 26 Kannan M. Moudgalya, Autumn 2007
26. Additional Properties of Fourier Transform
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26. Additional Properties of Fourier Transform
Recall
G e jw = G e jw
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26. Additional Properties of Fourier Transform
Recall
G e jw = G e jw
Symmetry of magnitude for real valued sequences
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26. Additional Properties of Fourier Transform
Recall
G e jw = G e jw
Symmetry of magnitude for real valued sequences
|G e jw | = G e jw G e jw1/ 2
= G e jw G e jw1/ 2
-
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G e G e
26. Additional Properties of Fourier Transform
Recall
G e jw = G e jw
Symmetry of magnitude for real valued sequences
|G e jw | = G e jw G e jw1/ 2
= G e jw G e jw1/ 2
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= |G (e jw ) |
26. Additional Properties of Fourier Transform
Recall
G e jw = G e jw
Symmetry of magnitude for real valued sequences
|G e jw | = G e jw G e jw1/ 2
= G e jw G e jw1/ 2
-
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= |G (e jw ) |
This shows that the magnitude is an even function.
26. Additional Properties of Fourier Transform
Recall
G e jw = G e jw
Symmetry of magnitude for real valued sequences
|G e jw | = G e jw G e jw1/ 2
= G e jw G e jw1/ 2
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= |G (e jw ) |
This shows that the magnitude is an even function. Similarly,
-
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26. Additional Properties of Fourier Transform
Recall
G e jw = G e jw
Symmetry of magnitude for real valued sequences
|G e jw | = G e jw G e jw1/ 2
= G e jw G e jw1/ 2
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= |G (e jw ) |
This shows that the magnitude is an even function. Similarly,
Arg G e jw
= Arg G e jw
Bode plots have to be drawn for w in [0, ] only.
Digital Control 27 Kannan M. Moudgalya, Autumn 2007
27. Sampling and Reconstruction
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27. Sampling and Reconstruction
u (n ) = u a (nT s ) , < n <
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27. Sampling and Reconstruction
u (n ) = u a (nT s ) , < n < Fast sampling:
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27. Sampling and Reconstruction
u (n ) = u a (nT s ) , < n < Fast sampling:
U a (F )1
u a ( t )
t F
F s2
F 0 F s
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F s2
T sF t
B B
F s2
32
F s3
2F s
u a (nT ) = u (n ) U F F sF s
F 0 + F sF 0
Digital Control 28 Kannan M. Moudgalya, Autumn 2007
28. Slow Sampling Results in Aliasing
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29. What to Do When Aliasing Cannot be Avoided?
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232/250
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30. Sampling Theorem
Suppose highest frequency contained in an analogsignal u a ( t ) is F max = B .
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30. Sampling Theorem
Suppose highest frequency contained in an analogsignal u a ( t ) is F max = B .
It is sampled at a rate F s > 2F max = 2 B .
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30. Sampling Theorem
Suppose highest frequency contained in an analogsignal u a ( t ) is F max = B .
It is sampled at a rate F s > 2F max = 2 B . u a ( t ) can be recovered from its sample values:
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30. Sampling Theorem
Suppose highest frequency contained in an analogsignal u a ( t ) is F max = B .
It is sampled at a rate F s > 2F max = 2 B . u a ( t ) can be recovered from its sample values:
( t )
( T )sin
Ts( t nT )
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u a ( t ) =n =
u a (nT s ) T s sT s ( t nT s )
30. Sampling Theorem
Suppose highest frequency contained in an analogsignal u a ( t ) is F max = B .
It is sampled at a rate F s > 2F max = 2 B . u a ( t ) can be recovered from its sample values:
( t )
( T )sin
Ts( t nT
s)
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240/250
u a ( t ) =n =
u a (nT s ) T s sT s ( t nT s )
If F s = 2 F max , F s is denoted by F N , theNyquist rate.
30. Sampling Theorem
Suppose highest frequency contained in an analogsignal u a ( t ) is F max = B .
It is sampled at a rate F s > 2F max = 2 B . u a ( t ) can be recovered from its sample values:
( t )
( T )sin
Ts( t nT
s)
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8/10/2019 Frequency Resposne
241/250
u a ( t ) =n =
u a (nT s ) T s sT s ( t nT s )
If F s = 2 F max , F s is denoted by F N , theNyquist rate.
Not causal: check n > 0Digital Control 31 Kannan M. Moudgalya, Autumn 2007
31. Rules for Sampling Rate Selection
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31. Rules for Sampling Rate Selection
Minimum sampling rate = twice band width
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31. Rules for Sampling Rate Selection
Minimum sampling rate = twice band width Shannons reconstruction cannot be implemented,
have to use ZOH
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244/250
31. Rules for Sampling Rate Selection
Minimum sampling rate = twice band width Shannons reconstruction cannot be implemented,
have to use ZOH Solution:
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245/250
31. Rules for Sampling Rate Selection
Minimum sampling rate = twice band width Shannons reconstruction cannot be implemented,
have to use ZOH Solution: sample faster
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246/250
31. Rules for Sampling Rate Selection
Minimum sampling rate = twice band width Shannons reconstruction cannot be implemented,
have to use ZOH Solution: sample faster
Number of samples in rise time = 4 to 10
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Number of samples in rise time = 4 to 10
31. Rules for Sampling Rate Selection
Minimum sampling rate = twice band width Shannons reconstruction cannot be implemented,
have to use ZOH Solution: sample faster
Number of samples in rise time = 4 to 10S l 10 30 i b d id h
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Number of samples in rise time = 4 to 10 Sample 10 to 30 times bandwidth
31. Rules for Sampling Rate Selection
Minimum sampling rate = twice band width Shannons reconstruction cannot be implemented,
have to use ZOH Solution: sample faster
Number of samples in rise time = 4 to 10S l 10 30 i b d id h
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249/250
Number of samples in rise time 4 to 10 Sample 10 to 30 times bandwidth Use 10 times Shannons sampling rate
31. Rules for Sampling Rate Selection
Minimum sampling rate = twice band width Shannons reconstruction cannot be implemented,
have to use ZOH Solution: sample faster
Number of samples in rise time = 4 to 10S l 10 t 30 ti b d idth
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250/250
Sample 10 to 30 times bandwidth Use 10 times Shannons sampling rate
cT s = 0 .15 to 0.5, where,c = crossover frequency
Digital Control 32 Kannan M. Moudgalya, Autumn 2007