ee70 review. electrical current circuit elements an electrical circuit consists of circuit elements...
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![Page 1: EE70 Review. Electrical Current Circuit Elements An electrical circuit consists of circuit elements such as voltage sources, resistances, inductances](https://reader037.vdocuments.us/reader037/viewer/2022102818/56649d6b5503460f94a49c21/html5/thumbnails/1.jpg)
EE70 Review
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Electrical Current
t
t
tqdttitq
dt
tdqti
0
)()()(
)()(
0
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Circuit Elements
An electrical circuit consists of circuit elements such as voltage sources, resistances, inductances and capacitances that are connected in closed paths by conductors
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Reference Directions
The voltage vab has a reference polarity that is positive at point a and negative at point b.
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Reference Directions
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“downhill: resistor”“uphill: battery”
Reference Directions
Energy is transferred when charge flows through an element having a voltage across it.
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2
1
)(
)()()(t
t
dttpw
titvtp Watts
Joules
Power and Energy
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• If current flows in the passive configuration the power is given by p = vi
• If the current flows opposite to the passive configuration, the power is given by p = -vi
Current is flowing in the passive
configuration
Reference Direction
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Dependent Sources
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Resistors and Ohm’s Law
Riv
iRv
abab
a
b
The units of resistance are Volts/Amp which are called “ohms”. The symbol for ohms is omega:
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A
LR
is the resistivity of the material used to fabricate the resistor. The units of resitivity are ohm-
meters (-m)
Resistance Related to Physical Parameters
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Power dissipation in a resistor
R
vRivip
22
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Kircohoff’s Current Law (KCL)
• The net current entering a node is zero
• Alternatively, the sum of the currents entering a node equals the sum of the currents leaving a node
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Kircohoff’s Current Law (KCL)
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Series Connection
cba iii
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Kircohoff’s Voltage Law (KVL)
The algebraic sum of the voltages equals zero for any closed path (loop) in an electrical circuit.
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Kircohoff’s Voltage Law (KVL)
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KVL through A and B: -va+vb = 0 va = vb
KVL through A and C: -va - vc = 0 va = -vc
Parallel Connection
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Equivalent Series Resistance
eqiRRRRiiRiRiRvvvv )( 321321321
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eqR
v
RRRv
R
v
R
v
R
viiii
321321321
111
Equivalent Parallel Resistance
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Circuit Analysis using Series/Parallel Equivalents
1. Begin by locating a combination of resistances that are in series or parallel. Often the place to start is farthest from the source.
2. Redraw the circuit with the equivalent resistance for the combination found in step 1.
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total321
111 v
RRR
RiRv
total321
222 v
RRR
RiRv
Of the total voltage, the fraction that appears across a given resistance in a series circuit is the ratio of the given resistance to the total series resistance.
Voltage Division
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total21
2
11 i
RR
R
R
vi
total21
1
22 i
RR
R
R
vi
For two resistances in parallel, the fraction of the total current flowing in a resistance is the ratio of the other resistance to the sum of the two resistances.
Current Division
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Node Voltage Analysis
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svv 1
03
32
4
2
2
12
R
vv
R
v
R
vv
03
23
5
3
1
13
R
vv
R
v
R
vv
Node Voltage Analysis
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Mesh Current Analysis
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Mesh Current Analysis
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Thévenin Equivalent Circuits
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oct vV
Thévenin Equivalent Circuits
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t
tsc R
Vi
Thévenin Equivalent Circuits
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sc
oc
i
vRt
Thévenin Equivalent Circuits
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Thévenin Equivalent Circuits
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Norton Equivalent Circuits
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scn iI
Norton Equivalent Circuits
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Source Transformations
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tLL
LL
Lt
tLLL
Lt
tL RR
dR
dPR
RR
VRiP
RR
VI
02
2
Maximum Power Transfer
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The superposition principle states that the total response is the sum of the responses to each of the independent sources acting individually. In equation form, this is
nT rrrr 21
Superposition Principle
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Superposition Principle
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Superposition Principle
VVvRR
Rv s 515
105
5
21
21
Current source open circuit
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Superposition Principle
Voltage source short circuit
VVVvvv
VAARR
RRiRiv
T
seqs
66.1166.65
66.6)33.3)(2(510
)5)(10()2(
21
21
212
Req
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The input resistance Ri is the equivalent resistance see when looking into the input terminals of the amplifier. Ro is the output resistance. Avoc is the open circuit voltage gain.
Voltage-Amplifier Model
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Ideally, an amplifier produces an output signal with identical waveshape as the input signal, but with a larger amplitude.
tvAtv ivo
Voltage Gain
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i
oi i
iA
L
iv
ii
Lo
i
oi R
RA
Rv
Rv
i
iA
Current Gain
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i
o
P
PG
L
iviv
ii
oo
i
o
R
RAAA
IV
IV
P
PG 2
Power Gain
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Operational Amplifier
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Operational amplifiers are almost always used with negative feedback, in which part of the output signal is returned to the input in opposition to the source signal.
Summing Point Constraint
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In a negative feedback system, the ideal op-amp output voltage attains the value needed to force the differential input voltage and input current to zero. We call this fact the summing-point constraint.
Summing Point Constraint
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1. Verify that negative feedback is present.
2. Assume that the differential input voltage and the input current of the op amp are forced to zero. (This is the summing-point constraint.)
3. Apply standard circuit-analysis principles, such as Kirchhoff’s laws and Ohm’s law, to solve for the quantities of interest.
Summing Point Constraint
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The Basic Inverter
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Applying the Summing Point Constraint
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1
2
in R
R
v
vA o
v
Inverting Amplifier
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Summing Amplifier
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1
2
in
1R
R
v
vA o
v
Non-inverting Amplifiers
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10
111
2
R
R
v
vA o
vin
Voltage Follower
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0
0
tqdttitqt
t
0
0
1tvdtti
Ctv
t
t
C
qv
v
qC
Capacitance
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Capacitances in Parallel
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Capacitances in Series
321
1111
CCCCeq
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Inductance
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The polarity of the voltage is such as to oppose the change in current (Lenz’s law).
Inductance
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Series Inductances
321 LLLLeq
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Parallel Inductances
321
11
LLLLeq
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Mutual InductanceFields are aiding Fields are opposing
Magnetic flux produced by one coil links the other coil
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Discharge of a Capacitance through a Resistance
0
R
tv
dt
tdvC CC
0 tvdt
tdvRC C
C
KCL at the top node of the circuit:
dt
dvC
dt
dqiCvq
v
qC C
iC iR
R
tvi CR
)(
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Discharge of a Capacitance through a Resistance
0 tvdt
tdvRC C
C
stC Ketv
0 stst KeRCKse
tvRCdt
tdvC
C 1
We need a function vC(t) that has the same form as it’s derivative.
Substituting this in for vc(t)
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RCs
1
RCtC Ketv
RCtiC eVtv iC Vv 0
Discharge of a Capacitance through a Resistance
Solving for s:
Substituting into vc(t):
Initial Condition: Full Solution:
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Discharge of a Capacitance through a Resistance
RCtiC eVtv iC Vv 0
RCtC Ketv
To find the unknown constant K, we need to use the boundary conditions at t=0. At t=0 the capacitor is initially charged to a voltage Vi and then discharges through the resistor.
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Discharge of a Capacitance through a Resistance
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Charging a Capacitance from a DC Source through a Resistance
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Charging a Capacitance from a DC Source through a Resistance
KCL at the node that joins the resistor and the capacitor
Current into the capacitor:
dt
dvC c
Current through the resistor:
R
Vtv SC )(
0)()(
R
Vtv
dt
tdvC SCC
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Charging a Capacitance from a DC Source through a Resistance
0)()(
R
Vtv
dt
tdvC SCC
Rearranging:
SCC Vtvdt
tdvRC )(
)(
This is a linear first-order differential equation with contant coefficients.
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Charging a Capacitance from a DC Source through a Resistance
The boundary conditions are given by the fact that the voltage across the capacitance cannot change instantaneously:
0)0()0( CC vv
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Charging a Capacitance from a DC Source through a Resistance
stC eKKtv 21)(
SCC Vtvdt
tdvRC )(
)(
Try the solution:
Substituting into the differential equation:
Gives:
Sst VKeKRCs 12)1(
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Charging a Capacitance from a DC Source through a Resistance
Sst VKeKRCs 12)1(
For equality, the coefficient of est must be zero:
RCsRCs
101
Which gives K1=VS
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Charging a Capacitance from a DC Source through a Resistance
RCtS
stC eKVeKKtv /
221)(
sSSC VKKVeKVv 220
2 0)0(
Substituting in for K1 and s:
Evaluating at t=0 and remembering that vC(0+)=0
RCtSS
stC eVVeKKtv /
21)(
Substituting in for K2 gives:
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tssC eVVtv
Charging a Capacitance from a DC Source through a Resistance
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DC Steady State
dt
tdvCti C
C)(
)(
In steady state, the voltage is constant, so the current through the capacitor is zero, so it behaves as an open circuit.
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DC Steady State
dt
tdiLtv L
L)(
)(
In steady state, the current is constant, so the voltage across and inductor is zero, so it behaves as a short circuit.
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The steps in determining the forced response for RLC circuits with dc sources are:
1. Replace capacitances with open circuits.
2. Replace inductances with short circuits.
3. Solve the remaining circuit.
DC Steady State
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RL Transient Analysis
S
S
Vdt
tdiLRti
tvRtiV
)(
)(
0)()(
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SVdt
tdiLRti
)()( steKKtiTry 21)(
Sst VesLKRKRK )( 221
AV
R
VKVRK S
S 250
10011
R
LssLKRK
022
steKKtiTry 21)( SVdt
tdiLRti
)()(
RL Transient Analysis
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)()()(
)()(
)(
)()()(
tftxdt
tdxR
tvti
dt
tdi
R
L
tvtRidt
tdiL
t
t
RC and RL Circuits with General Sources
First order differential equation with constant coefficients
Forcing function
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RC and RL Circuits with General Sources
The general solution consists of two parts.
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The particular solution (also called the forced response) is any expression that satisfies the equation.
In order to have a solution that satisfies the initial conditions, we must add the complementary solution to the particular solution.
)()()(
tftxdt
tdx
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The homogeneous equation is obtained by setting the forcing function to zero.
The complementary solution (also called the natural response) is obtained by solving the homogeneous equation.
0)()(
txdt
tdx
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Integrators produce output voltages that are proportional to the running time integral of the input voltages. In a running time integral, the upper limit of integration is t .
Integrators and Differentiators
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dttvRC
tvt
o in
0
1
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dt
dvRCtvo
in
Differentiator Circuit
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dt
tdvti
Cdt
tdiR
dt
tidL s )(
)(1)()(
2
2
Differentiating with respect to time:
tvvdttiC
tRidt
tdiL sC
t
01
0
Second–Order Circuits
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dt
tdv
Lti
LCdt
tdi
L
R
dt
tid s )(1)(
1)()(2
2
L
R
2
LC
10
Dampening coefficient
Undamped resonant frequency
dt
tdv
Ltf s )(1)(
)()()(
2)( 2
02
2
tftidt
tdi
dt
tid
Define:
Forcing function
Second–Order Circuits
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02
2
202
2
202
2
tidt
tdi
dt
tid
solutionaryComplement
tftidt
tdi
dt
tid
solutionParticular
Solution of the Second-Order Equation
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02
:
0)2(
:
02
:)(
20
2
20
2
20
2
ss
equationsticCharacteri
Kess
Factoring
KesKeKes
KetiTry
st
ststst
stC
02 202
2
tidt
tdi
dt
tid
Solution of the Complementary Equation
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0
20
21 s
20
22 s
Dampening ratio
Roots of the characteristic equation:
Solution of the Complementary Equation
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1. Overdamped case (ζ > 1). If ζ > 1 (or equivalently, if α > ω0), the roots of the characteristic equation are real and distinct. Then the complementary solution is:
tstsc eKeKti 21
21
In this case, we say that the circuit is overdamped.
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2. Critically damped case (ζ = 1). If ζ = 1 (or equivalently, if α = ω0 ), the roots are real and equal. Then the complementary solution
is
tstsc teKeKti 11
21
In this case, we say that the circuit is critically damped.
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3. Underdamped case (ζ < 1). Finally, if ζ < 1 (or equivalently, if α < ω0), the roots are complex. (By the term complex, we mean that the roots involve the square root of –1.) In other words, the roots are of the form:
nn jsjs 21 and
in which j is the square root of -1 and the natural frequency is given by:
220 n
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For complex roots, the complementary solution is of the form:
teKteKti nt
nt
c sincos 21
In this case, we say that the circuit is underdamped.
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Circuits with Parallel L and C
t
nL tiidttvL
tvRdt
tdvC
0
)()0()(1
)(1)(
We can replace the circuit with it’s Norton equivalent and then analyze the circuit by writing KCL at the top node:
dt
dvC
dt
dqiivdt
Li
R
Vi
t
cLLR 0
)0(1
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Circuits with Parallel L and C
dt
tdi
Ctv
LCdt
tdv
RCdt
tvd
dt
tditv
Ldt
tdv
Rdt
tvdC
atingdifferenti
tiidttvL
tvRdt
tdvC
n
n
t
nL
)(1)(
1)(1)(
)()(
1)(1)(
:
)()0()(1
)(1)(
2
2
0
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Circuits with Parallel L and C
)()()(
2)(
)(1)(
12
1
)(1)(
1)(1)(
20
2
0
2
tftvdt
tdv
dt
tvd
dt
tdi
CtffunctionForcing
LCfrequencyresonantUndamped
RCtcoefficienDampening
dt
tdi
Ctv
LCdt
tdv
RCdt
tvd
n
n
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Circuits with Parallel L and C
L
RcircuitSeries
RCcircuitParallel
tftvdt
tdv
dt
tvd
2
2
1
)()()(
2)( 2
0
2
This is the same equation as we found for the series LC circuit with the following changes for :
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LL Lj IV
90 LLjZ L
LLL Z IV
Complex Impedances-Inductor
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Complex Impedances-Inductor
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CCC Z IV
90111
CCjC
jZC
RR RIV
Complex Impedances-Capacitor
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Complex Impedances-Capacitor
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RR RIV
Impedances-Resistor
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Impedances-Resistor
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0321 VVV
We can apply KVL directly to phasors. The sum of the phasor voltages equals zero for any closed path.
The sum of the phasor currents entering a node must equal the sum of the phasor currents leaving.
outin II
Kirchhoff’s Laws in Phasor Form
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Power in AC Circuits
Z
VIwhereI
Z
V
Zm
mmm
0VI
For >0 the load is called “inductive” since Z=jL for an inductor
For <0 the load is “capacitive” since Z=-j/C for a capacitor
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Load Impedance in the Complex Plane
Z
X
Z
R
jXRZZ
)sin(
)cos(
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Power for a General Load
)cos(
)cos(
PF
IVP rmsrms
currentvoltage
Power angle:
If the phase angle for the voltage is not zero, we define the power angle :
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AC Power Calculations
WIVP cosrmsrms
VARIVQ sinrmsrms
Average Power:
Reactive Power:
Apparent Power: VAIV RMSRMS
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2rmsrms22 IVQP
Power Triangles
Average power
Reactive power
Average power
Apparent power
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The Thevenin equivalent for an ac circuit consists of a phasor voltage source Vt in series with a complex impedance Zt
Thevenin Equivalent Circuits
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The Thévenin voltage is equal to the open-circuit phasor voltage of the original circuit.
ocVV t
We can find the Thévenin impedance by zeroing the independent sources and determining the impedance looking into the circuit terminals.
Thevenin Equivalent Circuits
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The Thévenin impedance equals the open-circuit voltage divided by the short-circuit current.
scsc
oc
I
V
I
V ttZ
Thevenin Equivalent Circuits
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Norton Equivalent Circuit
The Norton equivalent for an ac circuit consists of a phasor current source In in parallel with a complex impedance Zt
scII n
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The Thevenin equivalent of a two-terminal circuit delivering power to a load impedance.
Maximum Average Power Transfer
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If the load can take on any complex value, maximum power transfer is attained for a load impedance equal to the complex conjugate of the Thévenin impedance.
If the load is required to be a pure resistance, maximum power transfer is attained for a load resistance equal to the magnitude of the Thévenin impedance.
Maximum Average Power Transfer
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Transfer Functions
The transfer function H(f ) of the two-port filter is defined to be the ratio of the phasor output voltage to the phasor input voltage as a function of frequency:
in
out
V
VfH
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First-Order Low Pass Filter
RCf
ffjfRCjfH
fCjRfCjfCj
fCjR
BBin
out
inout
in
2
1
)/(1
1
21
1)(
2
12
1
2
1
2
1
V
V
VIV
VI
Half power frequency
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BB
B
f
fff
ffjfH
arctan1
01
1
1
2
21
1
BfffH
Bf
ffH arctan
First-Order Low Pass Filter
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For low frequency signals the magnitude of the transfer function is unity and the phase is 0. Low frequency signals are passed while high frequency signals are attenuated and phase shifted.
First-Order Low Pass Filter
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Magnitude Bode Plot for First-Order Low Pass Filter
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1. A horizontal line at zero for f < fB /10.
2. A sloping line from zero phase at fB /10 to –90° at 10fB.
3. A horizontal line at –90° for f > 10fB.
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First-Order High-Pass Filter
fRCfwhere
ffj
ffj
fRCj
fRCj
fRCj
fCjR
R
BB
B
in
out
inininout
2
1
)/(1
)/(
12
2
2
11
1
2
1
V
V
VVVV
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First-Order High-Pass Filter
BB
B
B
BB
B
B
B
ffff
fH
ff
fffH
ffff
ff
ffj
ffjfH
arctan90arctan
90
1
arctan1
90
1
2
2in
out
V
V
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21 B
B
ff
fffH
BfffH arctan90
First-Order High-Pass Filter
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Bode Plots for the First-Order High-Pass Filter
0log10)log(20
)log(20
2
BBB
BB
fffffHffFor
fffHffFor
0
90
arctan90
0log10)log(20
)log(20
1log10)log(20
2
2
fHffFor
fHffFor
f
ffH
fffffHffFor
fffHffFor
fffffH
B
B
B
BBB
BB
BB
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Series Resonance
LCf
LCf
CfLf
resonanceFor
fCjRfLjfZ s
2
1
)2(
1
2
12
:
2
12)(
0
22
00
0
For resonance the reactance of the inductor and the capacitor cancel:
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Series Resonance
CRfQ
LCffrom
CfLSubstitute
R
LfResistance
resonance at inductance of ReactanceQ
s
s
0
020
2
0
2
1
2
1
)()2(
1
2
Quality factor QS
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Series Resonant Band-Pass Filter
f
f
f
fjQ
f
f
f
fjQ
R
f
f
f
fjQ
R
fZ
ss
R
s
sR
s
s
s
s
0
0
0
0
0
0
1
1
1
1
/
)(
V
VVIV
VVI
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ffffjQss
R
001
1
V
V
Series Resonant Band-Pass Filter
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Parallel Resonance
fLjfCjRZ p 2121
1
At resonance ZP is purely resistive:
LC
fLfjCfj
2
1212 000
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Parallel Resonance
CRfQ
LCffrom
CfLSubstitute
Lf
R
resonance at inductance of Reactance
ResistanceQ
P
P
0
020
2
0
2
2
1
)()2(
1
2
Quality factor QP
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Parallel Resonance
f
f
f
fjQ
RZ
P
Pout0
0
1
IIV Vout for constant current,
varying the frequency
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Second Order Low-Pass Filter
f
f
f
fjQ
ffjQ
LCfff
f
R
Lfj
fRC
j
fH
LCfff
f
R
Lfj
fRC
j
fC
jfLjR
fC
j
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Z
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S
in
out
inininCLR
Cout
0
0
0
00
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00
0
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)/(
2
121
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2
121
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22
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V
V
VVVV
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200
2
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002
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ffffQ
ffQfH
ffffQTanffffQ
ffQ
ffffjQ
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S
s
sS
s
s
s
in
out
V
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Second Order Low-Pass Filter
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Second Order Low-Pass Filter
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Second Order High-Pass Filter
At low frequency the capacitor is an open circuit
At high frequency the capacitor is a short and the inductor is open
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Second Order Band-Pass Filter
At low frequency the capacitor is an open circuit
At high frequency the inductor is an open circuit
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Second Order Band-Reject Filter
At low frequency the capacitor is an open circuit
At high frequency the inductor is an open circuit
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First-Order Low-Pass Filter
ffB
Bi
f
ffi
f
i
f
ff
ff
f
ff
f
f
ff
i
f
i
o
CRf
ffjR
R
CfRjR
R
Z
ZfH
CfRj
RZ
R
CfRj
RfCj
RZ
Z
Z
V
VfH
2
1
)/(1
1
21
1)(
21
21
2
1111
)(
A low-pass filter with a dc gain of -Rf/Ri
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First-Order High-Pass Filter
iiB
B
B
i
f
ii
if
i
i
ii
if
ii
f
i
f
ffi
ii
i
f
i
o
CRf
ffj
ffj
R
R
CRfj
CRfj
R
R
CRfj
CRfj
CfjR
R
Z
ZfH
RZCfj
RZ
Z
Z
v
vfH
2
1
)/(1
)/(
21
2
21
2
2
1)(
2
1
)(
A high-pass filter with a high frequency gain of -Rf/Ri
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N
BA
dA
AB
Magnetic flux passing through a surface area A:
For a constant magnetic flux density perpendicular to the surface:
The flux linking a coil with N turns:
Flux Linkages and Faraday’s Law
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Faraday’s law of magnetic induction:
dt
de
The voltage induced in a coil whenever its flux linkages are changing. Changes occur from:
• Magnetic field changing in time
• Coil moving relative to magnetic field
Faraday’s Law
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Lenz’s law states that the polarity of the induced voltage is such that the voltagewould produce a current (through an external resistance) that opposes the original change in flux linkages.
Lenz’s Law
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Lenz’s Law
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intensityfieldMagneticH HB
ytpermeabiliRelativer0
70 104
AmWb
Ampère’s Law: idlH
Magnetic Field Intensity and Ampère’s Law
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The line integral of the magnetic field intensity around a closed path is equal to the sum of the currents flowing through the surface bounded by the path.
Ampère’s Law
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Magnetic Field Intensity and Ampère’s Law
iHldlength lincrementa the as
direction samethe in points and magnitude
constant a has H field magnetic the If
productdotHdld
l
lH
)cos(
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In many engineering applications, we need to compute the magnetic fields for structures that lack sufficient symmetry for straight-forward application of Ampère’s law. Then, we use an approximate method known as magnetic-circuitanalysis.
Magnetic Circuits
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magnetomotive force (mmf) of an N-turn current-carrying coil
IN F
reluctance of a path for magnetic flux
A
R
RF
Analog: Voltage (emf)
Analog: Resistance
Analog: Ohm’s Law
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R
INr
NI
r
R
r
R
A
l
rARl
2
21211
2
2
22
2
RF
F
R
Magnetic Circuit for Toroidal Coil
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A Magnetic Circuit with Reluctances in Series and Parallel
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a
aa
a
aa
cba
ab
cba
ba
totalc
ba
ctotal
AB
AB
RR
R
dividercurrentRR
R
R
Ni
RR
RR
)(
111
A Magnetic Circuit with Reluctances in Series and Parallel
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1
11
1
111
i
iL
2
22
2
222
i
iL
2
12
2
21
1
21
1
12
iiiiM
Self inductance for coil 1
Self inductance for coil 2
Mutual inductance between coils 1 and 2:
Mutual Inductance
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Mutual Inductance
21222
12111
Total fluxes linking the coils:
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Currents entering the dotted terminals produce aiding fluxes
Mutual Inductance
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Circuit Equations for Mutual Inductance
dt
diL
dt
diM
dt
de
dt
diM
dt
diL
dt
de
iLMi
MiiL
22
122
211
11
2212
2111
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Ideal Transformers
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tvN
Ntv 1
1
22
)()( 12
12 ti
N
Nti
tptp 12
Ideal Transformers
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Mechanical Analog
12
121
2
12
11
221
1
22
)()( Fl
lFti
N
Nti
dl
ldtv
N
Ntv
d1
d2
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LL ZN
NZ
2
2
1
1
1
I
V
Impedance Transformations
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Semiconductor Diode
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Shockley Equation
breakdown reverse reaching until-for TDsD VvIi
1exp
T
DsD nV
vIi mV
q
kTVT 26
TVfor exp
D
T
DsD v
nV
vIi
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DDSS vRiV
Assume VSS and R are known. Find iD and vD
Load-Line Analysis of Diode Circuits
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DDSS vRiV DDSS vRiV
Load-Line Analysis of Diode Circuits
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The ideal diode acts as a shortcircuit for forward currentsand as an open circuit withreverse voltage applied.
iD > 0 vD < 0 diode is in the “on” state
vD < 0 ID = 0 diode is in the “off” state
Ideal Diode Model
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Assumed States for Analysis of Ideal-Diode Circuits
1. Assume a state for each diode, either on (i.e., a short circuit) or off (i.e., an open circuit). For n diodes there are 2n possible combinations of diode states.
2. Analyze the circuit to determine the current through the diodes assumed to be on and the voltage across the diodes assumed to be off.
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3. Check to see if the result is consistent with the assumed state for each diode. Current must flow in the forward direction for diodes assumed to be on. Furthermore, the voltage across the diodes assumed to be off must be positive at the cathode (i.e., reverse bias).
4. If the results are consistent with the assumed states, the analysis is finished. Otherwise, return to step 1 and choose a different combination of diode states.
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Half-Wave Rectifier with Resistive Load
The diode is on during the positive half of the cycle. The diode is off during the negative half of the cycle.
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CVVCTIQ rL The charge removed from the capacitor in one cycle:
Half-Wave Rectifier with Smoothing Capacitor
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r
L
V
TIC
2
The capacitance required for a full-wave rectifier is given by:
Full-Wave Rectifier
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Full-Wave Rectifier
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Clipper Circuit
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NPN Bipolar Junction Transistor
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Bias Conditions for PN Junctions
The base emitter p-n junction of an npn transistor is normally forward biased
The base collector p-n junction of an npn transistor is normally reverse biased
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Equations of Operation
1exp
T
BEESE V
vIi
BCE iii
From Kirchoff’s current law:
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Equations of Operation
E
C
i
i
Define as the ratio of collector current to emitter current:
Values for range from 0.9 to 0.999 with 0.99 being typical. Since:
EBBEBCE iiiiiii 01.099.0
Most of the emitter current comes from the collector and very little (1%) from the base.
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Equations of Operation
1B
C
i
i
Define as the ratio of collector current to base current:
Values for range from about 10 to 1,000 with a common value being 100.
BC ii
The collector current is an amplified version of the base current.
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Only a small fraction of the emitter current flows into the base provided that the collector-base junction is reverse biased and the base-emitter junction is forward biased.
The base region is very thin
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Common-Emitter Characteristics
biasreversevvif v
vvv
BCBECE
CEBEBC
0
vBC
vCE
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Common-Emitter Input Characteristics
1exp)1(
T
BEESB V
vIi
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Common-Emitter Output Characteristics
100 forii BC
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Amplification by the BJT
A small change in vBE results in a large change in iB if the base emitter is forward biased. Provided vCE is more than a few tenth’s of a volt, this change in iB results in a larger change in iC since iC=iB.
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Common-Emitter Amplifier
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Load-Line Analysis of a Common Emitter Amplifier (Input Circuit)
tvtiRtvV BEBBBB in
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Load-Line Analysis of a Common Emitter Amplifier (Output Circuit)
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As vin(t) goes positive, the load line moves upward and to the right, and the value of iB increases. This causes the operating point on the output to move upwards, decreasing vCE An increase in vin(t) results in a much larger decrease in vCE so that the common emitter amplifier is an inverting amplifier
Inverting Amplifier
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Except for reversal of current directions and voltage polarities, the pnp BJT is almost identical to the npn BJT.
PNP Bipolar Junction Transistor
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PNP Bipolar Junction Transistor
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NMOS Transistor
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NMOS Transistor
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Operation in the Cutoff Region
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By applying a positive bias between the Gate (G) and the body (B), electrons are attracted to the gate to form a conducting n-type channel between the source and drain. The positive charge on the gate and the negative charge in the channel form a capacitor where:
Operation Slightly Above Cut-Off
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For small values of vDS, iD is proportional to vDS. The device behaves as a resistance whose value depends on vGS.
Operation Slightly Above Cut-Off
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Operation in the Triode Region
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Load-Line Analysis of a Simple NMOS Circuit
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Load-Line Analysis of a Simple NMOS Circuit
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Load-Line Analysis of a Simple NMOS Circuit
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CMOS Inverter
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Two-Input CMOS NAND Gate
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Two-Input CMOS NOR Gate