Download - DC to AC Conversion (INVERTER ) - ENCON
Power Electronics and Drives (Version 2): Dr.
Zainal Salam, 2002
1
Chapter 4DC to AC Conversion
(INVERTER)• General concept• Basic principles/concepts• Single-phase inverter
– Square wave– Notching– PWM
• Harmonics• Modulation• Three-phase inverter
Power Electronics and Drives (Version 2): Dr.
Zainal Salam, 2002
2
DC to AC Converter (Inverter)
• DEFINITION: Converts DC to AC power by switching the DC input voltage (or current) in a pre-determined sequence so as to generate AC voltage (or current) output.
• TYPICAL APPLICATIONS:– Un-interruptible power supply (UPS), Industrial
(induction motor) drives, Traction, HVDC
• General block diagram
IDC Iac
+
−
VDC Vac
+
−
Power Electronics and Drives (Version 2): Dr.
Zainal Salam, 2002
3
Types of inverter
• Voltage Source Inverter (VSI)• Current Source Inverter (CSI)
"DC LINK" Iac
+
−
VDC Load Voltage
+
−
L ILOAD
Load CurrentIDC+
−
VDC
C
Power Electronics and Drives (Version 2): Dr.
Zainal Salam, 2002
4
Voltage source inverter (VSI) with variable DC link
DC LINK
+
-
Vs Vo
+
-
C+
-Vin
CHOPPER(Variable DC output)
INVERTER(Switch are turned ON/OFFwith square-wave patterns)
• DC link voltage is varied by a DC-to DC converter or controlled rectifier.
• Generate “square wave” output voltage.
• Output voltage amplitude is varied as DC link is varied.
• Frequency of output voltage is varied by changing the frequency of the square wave pulses.
Power Electronics and Drives (Version 2): Dr.
Zainal Salam, 2002
5
Variable DC link inverter (2)
• Advantages:– simple waveform generation– Reliable
• Disadvantages:– Extra conversion stage– Poor harmonics
T1 T2 t
Vdc1
Vdc2 Higher input voltageHigher frequency
Lower input voltageLower frequency
Power Electronics and Drives (Version 2): Dr.
Zainal Salam, 2002
6
VSI with fixed DC link INVERTER
+
−
Vin
(fixed)Vo
+
−
C
Switch turned ON and OFFwith PWM pattern
• DC voltage is held constant.
• Output voltage amplitude and frequency are varied simultaneously using PWM technique.
• Good harmonic control, but at the expense of complex waveform generation
Power Electronics and Drives (Version 2): Dr.
Zainal Salam, 2002
7
Operation of simple square-wave inverter (1)
• To illustrate the concept of AC waveform generation
VDC
T1
T4
T3
T2
+ VO -
D1
D2
D3
D4
SQUARE-WAVEINVERTERS
S1 S3
S2S4
EQUAVALENTCIRCUIT
IO
Power Electronics and Drives (Version 2): Dr.
Zainal Salam, 2002
8
Operation of simple square-wave inverter (2)
VDC
S1
S4
S3
+ vO −
VDC
S1
S4
S3
S2
+ vO −
VDC
vO
t1 t2
t
S1,S2 ON; S3,S4 OFF for t1 < t < t2
t2 t3
vO
-VDC
t
S3,S4 ON ; S1,S2 OFF for t2 < t < t3
S2
Power Electronics and Drives (Version 2): Dr.
Zainal Salam, 2002
9
Waveforms and harmonics of square-wave inverter
FUNDAMENTAL
3RD HARMONIC
5RD HARMONIC
πDCV4
Vdc
-Vdc
V1
31V
51V
INVERTEROUTPUT
Power Electronics and Drives (Version 2): Dr.
Zainal Salam, 2002
10
Filtering• Output of the inverter is “chopped AC
voltage with zero DC component”.In some applications such as UPS, “high purity” sine wave output is required.
• An LC section low-pass filter is normally fitted at the inverter output to reduce the high frequency harmonics.
• In some applications such as AC motor drive, filtering is not required.
vO 1
+
−
LOAD
L
CvO 2
(LOW PASS) FILTER
+
−
vO 1 vO 2
Power Electronics and Drives (Version 2): Dr.
Zainal Salam, 2002
11
Notes on low-pass filters• In square wave inverters, maximum output voltage
is achievable. However there in NO control in harmonics and output voltage magnitude.
• The harmonics are always at three, five, seven etc times the fundamental frequency.
• Hence the cut-off frequency of the low pass filter is somewhat fixed. The filter size is dictated by the VA ratings of the inverter.
• To reduce filter size, the PWM switching schemecan be utilised.
• In this technique, the harmonics are “pushed” to higher frequencies. Thus the cut-off frequency of the filter is increased. Hence the filter components (I.e. L and C) sizes are reduced.
• The trade off for this flexibility is complexity in the switching waveforms.
Power Electronics and Drives (Version 2): Dr.
Zainal Salam, 2002
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“Notching”of square wave
Vdc
Vdc−
Vdc
Vdc−
Notched Square Wave
Fundamental Component
• Notching results in controllable output voltage magnitude (compare Figures above).
• Limited degree of harmonics control is possible
Power Electronics and Drives (Version 2): Dr.
Zainal Salam, 2002
13
Pulse-width modulation (PWM)
• A better square wave notching is shown below - this is known as PWM technique.
• Both amplitude and frequency can be controlled independently. Very flexible.
1
1 pwm waveform
desired sinusoid
SINUSOIDAL PULSE-WITDH MODULATEDAPPROXIMATION TO SINE WAVE
Power Electronics and Drives (Version 2): Dr.
Zainal Salam, 2002
14
PWM- output voltage and frequency control
Power Electronics and Drives (Version 2): Dr.
Zainal Salam, 2002
15
Output voltage harmonics• Why need to consider harmonics?
– Waveform quality must match TNB supply. “Power Quality” issue.
– Harmonics may cause degradation of equipment. Equipment need to be “de-rated”.
• Total Harmonic Distortion (THD) is a measure to determine the “quality” of a given waveform.
• DEFINITION of THD (voltage)
( ) ( ) ( )
( )
frequency. harmonicat impedance theis
:current harmonic with voltageharmonic thereplacingby obtained becan THDCurrent
number. harmonics theis where
,1
2
2,
,1
2
2,1
2
,1
2
2,
nn
nn
RMS
nRMSn
RMS
nRMSRMS
RMS
nRMSn
ZZVI
I
ITHDi
n
V
VV
V
VTHDv
=
=
−
==
∑
∑∑
∞
=
∞
=
∞
=
Power Electronics and Drives (Version 2): Dr.
Zainal Salam, 2002
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Fourier Series
• Study of harmonics requires understanding of wave shapes. Fourier Series is a tool to analyse wave shapes.
( )
( )
( )t
nbnaavf
dnvfb
dnvfa
dvfa
nnno
n
n
o
ωθ
θθ
θθπ
θθπ
θπ
π
π
π
=
++=
=
=
=
∑
∫
∫
∫
∞
= where
sincos21)(
Fourier Inverse
sin)(1
cos)(1
)(1
SeriesFourier
1
2
0
2
0
2
0
Power Electronics and Drives (Version 2): Dr.
Zainal Salam, 2002
17
Harmonics of square-wave (1)
Vdc
-Vdc
θ=ωtπ 2π
( ) ( )
( ) ( )
−=
=
−=
=
−+=
∫∫
∫∫
∫∫
π
π
π
π
π
π
π
π
π
θθθθπ
θθθθπ
θθπ
2
0
2
0
2
0
sinsin
0coscos
01
dndnVb
dndnVa
dVdVa
dcn
dcn
dcdco
Power Electronics and Drives (Version 2): Dr.
Zainal Salam, 2002
18
Harmonics of square wave (2)
( ) ( )[ ][ ]
[ ]
[ ]
π
π
π
ππ
πππ
ππππ
θθπ
ππ
π
nVb
n
bn
nnV
nnnV
nnnnV
nnnVb
dcn
n
dc
dc
dc
dcn
41cos odd, isn when
01cos even, isn when
)cos1(2)cos1()cos1(
)cos2(cos)cos0(cos
coscos
Solving,
20
=
=
−=
=
−=
−+−=
−+−=
+−=
Power Electronics and Drives (Version 2): Dr.
Zainal Salam, 2002
19
Spectra of square wave
1 3 5 7 9 11
NormalisedFundamental
3rd (0.33)
5th (0.2)7th (0.14)
9th (0.11)11th (0.09)
1st
n
• Spectra (harmonics) characteristics:– Harmonic decreases as n increases. It decreases
with a factor of (1/n). – Even harmonics are absent– Nearest harmonics is the 3rd. If fundamental is
50Hz, then nearest harmonic is 150Hz.– Due to the small separation between the
fundamental an harmonics, output low-pass filter design can be quite difficult.
Power Electronics and Drives (Version 2): Dr.
Zainal Salam, 2002
20
Quasi-square wave (QSW)
( ) [ ]( ) ( )[ ]
( ) ( )
απαπαπ
απαπ
απαπ
θπ
θθπ
απα
απ
α
nnnnnn
nnn
nnnV
nnVdnVb
a
dc
dcdcn
n
coscossinsincoscos
coscos
Expanding,
coscos2
cos2sin12
symmetry, wave-half toDue
.0 that Note
=+=
−=−
−−=
−=
=
=
−−
∫
π π2
α α αVdc
-Vdc
Power Electronics and Drives (Version 2): Dr.
Zainal Salam, 2002
21
Harmonics control
( )[ ]
( )[ ]
( )
( )
n
n
b
b
Vb
nnVb
b
nnnV
nnnnVb
o
dc
dcn
n
dc
dcn
o
3
1
1
90:if eliminated be will harmonic general,
In waveform. thefrom eliminated is harmonic thirdor the,0then ,30 if exampleFor , adjustingby controlled be alsocan Harmonics
α by varying controlled is ,, lfundamenta The
cos4:is lfundamenta theof amplitude ,particularIn
cos4 odd, isn If
,0 even, isn If
cos1cos2coscoscos2
=
==
=
=⇒
=⇒
−=
−=⇒
α
αα
απ
απ
παπ
απαπ
Power Electronics and Drives (Version 2): Dr.
Zainal Salam, 2002
22
Example
degrees30 with case wavesquare-quasifor (c) and (b)Repeat
harmonics zero-non efirst thre theusingby THDi thec)harmonics zero-non efirst thre theusingby THDv theb)
formula. exact"" theusing THDv thea):Calculate series.in 10mHL and
10RR is load The 100V. is gelink volta DC The signals. wavesquareby fed isinverter phase single bridge-fullA
=
==
α
Power Electronics and Drives (Version 2): Dr.
Zainal Salam, 2002
23
Half-bridge inverter (1)
Vo
RL
+−
VC1
VC2
+
-
+
-S1
S2
Vdc
2Vdc
2Vdc
−
S1 ONS2 OFF
S1 OFFS2 ON
t0G
• Also known as the “inverter leg”.• Basic building block for full bridge, three
phase and higher order inverters.• G is the “centre point”.• Both capacitors have the same value.
Thus the DC link is equally “spilt”into two.
Power Electronics and Drives (Version 2): Dr.
Zainal Salam, 2002
24
Half-bridge inverter (2)
• The top and bottom switch has to be “complementary”, i.e. If the top switch is closed (on), the bottom must be off, and vice-versa.
• In practical, a dead time as shown below is required to avoid “shoot-through” faults.
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td td
"Dead time' = td
S1signal(gate)
S2signal(gate)
S1
S2
+
−
Vdc
RL
G
"Shoot through fault" .Ishort is very large
Ishort
Power Electronics and Drives (Version 2): Dr.
Zainal Salam, 2002
25
Single-phase, full-bridge (1)
• Full bridge (single phase) is built from two half-bridge leg.
• The switching in the second leg is “delayed by 180 degrees” from the first leg.
S1
S4
S3
S2
+
-
G
+
2dcV
2dcV
-
2dcV
2dcV
dcV
2dcV
−
2dcV
−
dcV−
π
π
π
π2
π2
π2
tω
tω
tω
RGV
GRV '
oV
GRo VVVRG '−=
groumd" virtual" is G
LEG R LEG R'
R R'- oV+
dcV
+
-
Power Electronics and Drives (Version 2): Dr.
Zainal Salam, 2002
26
Three-phase inverter
• Each leg (Red, Yellow, Blue) is delayed by 120 degrees.
• A three-phase inverter with star connected load is shown below
ZYZR ZB
G R Y B
iR iYiB
ia ib
+Vdc
N
S1
S4 S6
S3 S5
S2
+
+
−
−
Vdc/2
Vdc/2
Power Electronics and Drives (Version 2): Dr.
Zainal Salam, 2002
27
Square-wave inverter waveforms
13
2,4
23,54
35
4,6
41,56
51
2,6
61,32
VAD
VB0
VC0
VAB
VAPH
(a) Three phase pole switching waveforms
(b) Line voltage waveform
(c) Phase voltage waveform (six-step)
600 1200
IntervalPositive device(s) on
Negative devise(s) on
2VDC/3VDC/3
-VDC/3-2VDC/3
VDC
-VDC
VDC/2
-VDC/2t
t
t
t
t
Quasi-square wave operation voltage waveforms
Power Electronics and Drives (Version 2): Dr.
Zainal Salam, 2002
28
Three-phase inverter waveform relationship
• VRG, VYG, VBG are known as “pole switching waveform” or “inverter phase voltage”.
• VRY, VRB, VYB are known as “line to line voltage” or simply “line voltage”.
• For a three-phase star-connected load, the load phase voltage with respect to the “N” (star-point) potential is known as VRN ,VYN,VBN. It is also popularly termed as “six-step” waveform
Power Electronics and Drives (Version 2): Dr.
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29
MODULATION: Pulse Width Modulation (PWM)
Modulating Waveform Carrier waveform
1M1+
1−
0
2dcV
2dcV
−
00t 1t 2t 3t 4t 5t
• Triangulation method (Natural sampling)– Amplitudes of the triangular wave (carrier) and
sine wave (modulating) are compared to obtain PWM waveform. Simple analogue comparator can be used.
– Basically an analogue method. Its digital version, known as REGULAR sampling is widely used in industry.
Power Electronics and Drives (Version 2): Dr.
Zainal Salam, 2002
30
PWM types
• Natural (sinusoidal) sampling (as shown on previous slide)– Problems with analogue circuitry, e.g. Drift,
sensitivity etc.
• Regular sampling– simplified version of natural sampling that
results in simple digital implementation
• Optimised PWM– PWM waveform are constructed based on
certain performance criteria, e.g. THD.
• Harmonic elimination/minimisation PWM– PWM waveforms are constructed to eliminate
some undesirable harmonics from the output waveform spectra.
– Highly mathematical in nature
• Space-vector modulation (SVM)– A simple technique based on volt-second that is
normally used with three-phase inverter motor-drive
Power Electronics and Drives (Version 2): Dr.
Zainal Salam, 2002
31
Natural/Regular sampling
( )
(1,2,3...)integer an is and signal modulating theoffrequency theis where
M
:at locatednormally are harmonics The .frequency" harmonic" the torelated is M
waveformmodulating theofFrequency veformcarrier wa theofFrequency M
)(MRATIO MODULATION
ly.respective voltage,(DC)input and voltageoutput theof lfundamenta are , where
M
:holds iprelationshlinear the1, M0 If
versa. viceandhigh isoutput wavesine the thenhigh, isM If magnitude. tageoutput vol
wave)(sine lfundamenta the torelated is M
veformcarrier wa theof Amplitude waveformmodulating theof AmplitudeM
:MINDEX MODULATION
R
R
R
R
1
I1
I
II
I
I
kf
fkf
p
p
VV
VV
m
m
in
in
=
==
==−−−−−−−−−−−−−−−−−−−−−−−−−−−−
=
<<
=
=
Power Electronics and Drives (Version 2): Dr.
Zainal Salam, 2002
32
Asymmetric and symmetric regular sampling
T
samplepoint
tM mωsin11+
1−
4T
43T
45T
4π
2dcV
2dcV
−
0t 1t 2t 3tt
asymmetric sampling
symmetricsampling
t
Generating of PWM waveform regular sampling
Power Electronics and Drives (Version 2): Dr.
Zainal Salam, 2002
33
Bipolar and unipolar PWM switching scheme
• In many books, the term “bipolar” and “unipolar” PWM switching are often mentioned.
• The difference is in the way the sinusoidal (modulating) waveform is compared with the triangular.
• In general, unipolar switching scheme produces better harmonics. But it is more difficult to implement.
• In this class only bipolar PWM is considered.
Power Electronics and Drives (Version 2): Dr.
Zainal Salam, 2002
34
Bipolar PWM switching
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����������
k1δk2δ
kα
∆4∆
=δ
π π2
carrierwaveform
modulatingwaveform
pulsekth
π π2
Power Electronics and Drives (Version 2): Dr.
Zainal Salam, 2002
35
Pulse width relationships
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����������
k1δk2δ
kα
∆4∆
=δ
π π2
carrierwaveform
modulatingwaveform
pulsekth
π π2
Power Electronics and Drives (Version 2): Dr.
Zainal Salam, 2002
36
Characterisation of PWM pulses for bipolar switching
pulse PWMkth The
∆
0δ 0δ 0δ 0δ
k1δk2δ
2SV+
2SV
−
kα
Power Electronics and Drives (Version 2): Dr.
Zainal Salam, 2002
37
Determination of switching angles for kth PWM pulse (1)
v Vmsin θ( )
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Ap2Ap1
2dcV+
2dcV
−
AS2
AS1
22
11
second,- volt theEquating
ps
ps
AA
AA
=
=
Power Electronics and Drives (Version 2): Dr.
Zainal Salam, 2002
38
PWM Switching angles (2)
[ ]
)sin(sin2
cos)2cos(sin
sinusoid, by the supplied second- voltThe
where; 2
Similarly,
where
22
2)2(
2
:asgiven is pulse PWM theof cycle halfeach during voltageaverage The
21
2222
11
11
111
okom
kokmms
o
okk
dckk
o
okk
sk
o
okdc
o
kokdck
V
VdVA
VV
VV
VV
k
ok
δαδ
αδαθθ
δδδ
ββ
δδδ
β
βδ
δδδ
δδδ
α
δα
−=
−−==
−=
=
−=
=
−
=
−−
=
∫−
Power Electronics and Drives (Version 2): Dr.
Zainal Salam, 2002
39
Switching angles (3)
)sin()2(
)sin(222
edge leading for the Hence,
;strategy, modulation thederive To
22
;22
, waveformsPWM theof seconds- voltThe
)sin(2Similarly,
)sin(2, smallfor sin
Since,
1
1
2211
21211
2
1
okdc
mk
okmoodc
k
spsp
odc
kpodc
kp
okmos
okmosooo
VV
VV
AAAA
VAVA
VA
VA
δαβ
δαδδβ
δβδβ
δαδ
δαδδδδ
−=⇒
−=
==
=
=
+=
−=→
Power Electronics and Drives (Version 2): Dr.
Zainal Salam, 2002
40
PWM switching angles (4)
[ ]
[ ])sin(1 and
)sin(1
width,-pulse for the solve tongSubstituti
)sin(
:derived becan edge trailing themethod,similar Using
)sin(
Thus,
1. to0 from It varies depth.or index
modulation asknown is 2
ratio, voltageThe
2
1
11
2
1
okIok
okIoko
okk
okIk
okIk
dc
mI
M
M
M
M
)(VVM
δαδδ
δαδδδ
δδβ
δαβ
δαβ
++=
−+=⇒
−=
−=
−=
=
Power Electronics and Drives (Version 2): Dr.
Zainal Salam, 2002
41
PWM Pulse width
[ ]kIok
kk
kk
M αδδ
δδδδδ
δα
δα
sin1
,Modulation SymmetricFor different. are andi.e ,Modulation
Asymmetricfor validisequation above The
:edge Trailing
:edge Leading
:is pulsekth theof angles switching theThus
k 2k 1k 2k 1k
1
1
+=⇒
==
+
−
Power Electronics and Drives (Version 2): Dr.
Zainal Salam, 2002
42
Example• For the PWM shown below, calculate the switching
angles for all the pulses.
V5.1V2
π π2
1 2 3 4 5 6 7 8 9
t1 t2 t3 t4 t5 t6 t7 t8 t9 t10 t11 t12t13
t14t15
t16t17
t18 π2π
1α
carrierwaveform
modulatingwaveform
Power Electronics and Drives (Version 2): Dr.
Zainal Salam, 2002
43
Harmonics of bipolar PWM
{
})2(cos)(cos )(cos)(cos )(cos)2(cos
: toreduced becan Which
sin2
2
sin2
2
sin2
2
sin)(12
:as computed becan pulse PWM (kth)each ofcontent harmonicsymmetry,
wave-half is waveformPWM theAssuming
212
1
2
2
0
2
2
1
1
okkkkkkk
kkokdc
nk
dc
dc
dc
T
nk
nnnnnn
nV b
dnV
dnV
dnV
dnvfb
ok
kk
kk
kk
kk
ok
δαδαδαδα
δαδαπ
θθπ
θθπ
θθπ
θθπ
δα
δα
δα
δα
δα
δα
+−++−−++
−−−−=
−+
+
−=
=
∫
∫
∫
∫
+
+
+
−
−
−
Power Electronics and Drives (Version 2): Dr.
Zainal Salam, 2002
44
Harmonics of PWM
[]
equation. thisofn computatio
theshows pagenext on the slide The
:i.e. period, oneover pulses for the of sum isthe waveformPWM
for the coefficentFourier ly.Theproductive simplified becannot equation This
2coscos2 )2(cos)(cos2
Yeilding,
1
11
∑=
=
+
−−−=
p
knkn
nk
ok
kkkkdc
nk
bb
pb
nnnn
nVb
δα
αδαπ
Power Electronics and Drives (Version 2): Dr.
Zainal Salam, 2002
45
PWM Spectra
p p2 p3 p40.1=M
8.0=M
6.0=M
4.0=M
2.0=M
Amplitude
Fundamental
0
2.0
4.0
6.0
8.0
0.1
NORMALISED HARMONIC AMPLITUDES FORSINUSOIDAL PULSE-WITDH MODULATION
Depth ofModulation
Power Electronics and Drives (Version 2): Dr.
Zainal Salam, 2002
46
PWM spectra observations
• The amplitude of the fundamental decreases or increases linearly in proportion to the depth of modulation (modulation index). The relation ship is given as: V1= MIVin
• The harmonics appear in “clusters” with main components at frequencies of : f = kp (fm); k=1,2,3.... where fm is the frequency of the modulation (sine) waveform. This also equal to the multiple of the carrier frequencies. There also exist “side-bands” around the main harmonic frequencies.
• The amplitude of the harmonic changes with MI. Its incidence (location on spectra) is not.
• When p>10, or so, the harmonics can be normalised as shown in the Figure. For lower values of p, the side-bands clusters overlap, and the normalised results no longer apply.
Power Electronics and Drives (Version 2): Dr.
Zainal Salam, 2002
47
Bipolar PWM Harmonics
h MI
0.2 0.4 0.6 0.8 1.0
1 0.2 0.4 0.6 0.8 1.0
MR 1.242 1.15 1.006 0.818 0.601
MR +2 0.016 0.061 0.131 0.220 0.318
MR +4 0.018
2MR +1 0.190 0.326 0.370 0.314 0.181
2MR +3 0.024 0.071 0.139 0.212
2MR +5 0.013 0.033
3MR 0.335 0.123 0.083 0.171 0.113
3MR +2 0.044 0.139 0.203 0.716 0.062
3MR +4 0.012 0.047 0.104 0.157
3MR +6 0.016 0.044
4MR +1 0.163 0.157 0.008 0.105 0.068
4MR +3 0.012 0.070 0.132 0.115 0.009
4MR+5 0.034 0.084 0.1194MR +7 0.017 0.050
Power Electronics and Drives (Version 2): Dr.
Zainal Salam, 2002
48
Bipolar PWM harmonics calculation example
( )
harmonics.dominant theof some and voltagefrequency -lfundamenta theof valuestheCalculate 47Hz. is lfrequencyfundamenta
The 39.M 0.8,M 100V,V inverter, PWM phase single bridge-full In the
:Example
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PWM,bipolar phase-single bridge fullfor :Note
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Power Electronics and Drives (Version 2): Dr.
Zainal Salam, 2002
49
Three-phase harmonics: “Effect of odd triplens”
• For three-phase inverters, there is significant advantage if p is chosen to be:
– odd and multiple of three (triplens) (e.g. 3,9,15,21, 27..)
– the waveform and harmonics and shown on the next two slides. Notice the difference?
• By observing the waveform, it can be seen that with odd p, the line voltage shape looks more “sinusoidal”.
• The even harmonics are all absent in the phase voltage (pole switching waveform). This is due to the p chosen to be odd.
Power Electronics and Drives (Version 2): Dr.
Zainal Salam, 2002
50
Spectra observations
• Note the absence of harmonics no. 21, 63 in the inverter line voltage. This is due to p which is multiple of three.
• In overall, the spectra of the line voltage is more “clean”. This implies that the THD is less and the line voltage is more sinusoidal.
• It is important to recall that it is the line voltage that is of the most interest.
• Also can be noted from the spectra that the phase voltage amplitude is 0.8 (normalised). This is because the modulation index is 0.8. The line voltage amplitude is square root three of phase voltage due to the three-phase relationship.
Power Electronics and Drives (Version 2): Dr.
Zainal Salam, 2002
51
Waveform: effect of “triplens”2dcV
2dcV
−
2dcV
2dcV
−
2dcV
−
2dcV
−
2dcV
2dcV
dcV
dcV
dcV−
dcV−
π π2
RGV
RGV
RYV
RYV
YGV
YGV
6.0,8 == Mp
6.0,9 == MpILLUSTRATION OF BENEFITS OF USING A FREQUENCY RATIOTHAT IS A MULTIPLE OF THREE IN A THREE PHASE INVERTER
Power Electronics and Drives (Version 2): Dr.
Zainal Salam, 2002
52
Harmonics: effect of “triplens”
0
2.0
4.0
6.0
8.0
0.1
2.1
4.1
6.1
8.1
Amplitude
voltage)line to(Line 38.0
Fundamental
41 4339
3745
472319
21 63
6159
5765
6769 77
798183 85
8789
91
19 2343
4741
3761
5965
6783
7985
89
COMPARISON OF INVERTER PHASE VOLTAGE (A) & INVERTER LINE VOLTAGE(B) HARMONIC (P=21, M=0.8)
A
B
Harmonic Order
Power Electronics and Drives (Version 2): Dr.
Zainal Salam, 2002
53
Comments on PWM scheme
• It is desirable to push p to as large as possible.
• The main impetus for that when p is high, then the harmonics will be at higher frequencies because frequencies of harmonics are related to: f = kp(fm), wherefm is the frequency of the modulating signal.
• Although the voltage THD improvement is not significant, but the current THD will improve greatly because the load normally has some current filtering effect.
• In any case, if a low pass filter is to be fitted at the inverter output to improve the voltage THD, higher harmonic frequencies is desirable because it makes smaller filter component.
Power Electronics and Drives (Version 2): Dr.
Zainal Salam, 2002
54
ExampleThe amplitudes of the pole switching waveform harmonics of the redphase of a three-phase inverter is shown in Table below. The inverter uses a symmetric regular sampling PWM scheme. The carrier frequencyis 1050Hz and the modulating frequency is 50Hz. The modulationindex is 0.8. Calculate the harmonic amplitudes of the line-to-voltage(i.e. red to blue phase) and complete the table.
Harmonic number
Amplitude (pole switching waveform)
Amplitude (line-to line voltage)
1 1
19 0.3
21 0.8
23 0.3
37 0.1
39 0.2
41 0.25
43 0.25
45 0.2
47 0.1
57 0.05
59 0.1
61 0.15
63 0.2
65 0.15
67 0.1
69 0.05