d. budimir; westminster university...

WCRG Wireless CommunicationsWCRG Research Group

DESIGN OF MICROWAVE DIGITALDESIGN OF MICROWAVE DIGITAL RADIO TRANSCEIVER FRONT ENDS

Assoc. Prof. D. Budimir Wi l C i ti R h G S h l f El t iWireless Communications Research Group,School of Electronics

and Computer Science, University of Westminster, London W1W 6UW, UK

Email: [email protected]

D. Budimir; Westminster University London

WCRG Wireless CommunicationsResearch Group

Wireless System: EXAMPLE


Utility private network diagram


TV distribution network diagramD. Budimir; Westminster University London

g

Carrier network diagram


Mobile cellular backhaul network diagram


D. Budimir; Westminster University LondonTypical Microwave Dish Towers

Typical Microwave Dish Towers



D. Budimir; Westminster University London9

RF and Microwave Filters - Applications

Mobile Cellular RadioWireless CommunicationsSpace and Satellite CommunicationsRadar Systems

Block diagram of a typical radiotransceiver front end

Block diagram of the communicationl d f lli


payload of a satellite

According to the Nokia-Siemens, M bil B db d b ib d d 4 4billi i 2015Mobile Broadband subscribers exceeded 4.4billion in 2015 Today in Europe: 984million2015 in Europe: 1.5billionFixed Broadband subscribers exceeded 2 4billion in 2015Fixed Broadband subscribers exceeded 2.4billion in 2015 Today in Europe: 143million2015 in Europe: 214millionDevices: 2015Devices: 2015Mobile phones: 2.5billionSmart phones: Laptops: 250millionLaptops: 250million

According to the Wi-Fi Alliance (http://www.wi-fi.org/),

Wi-Fi chipset sales exceeded 200million units in 2006 and are expected to grow to 500million units by 2009.The highlights are as follows: g gGSM subscribers reached 2,278,095,380WCDMA subscribers reached 114,664,827cdmaOne had 36,280,000 subscribers,


CDMA2000 had 350,820,000 subscribers,

According to the Nokia-SiemensAccording to the Nokia Siemens,

Mobile Broadband subscribers exceeded 4.4billion in 2015 Today in Europe: 984millionToday in Europe: 984million2015 in Europe: 1.5billion

2 4billiFixed Broadband subscribers exceeded 2.4billion in 2015 Today in Europe: 143million2015 in Europe: 214million2015 in Europe: 214millionDevices: 2015Mobile phones: 2.5billionS t hSmart phones: Laptops : 250million


According to the Wi-Fi Alliance (http://www.wi-fi.org/),

Wi-Fi chipset sales exceeded 200million unitsin 2006

and are expected to grow to 500millionunits by 2009.

The highlights are as follows: GSM subscribers reached 2,278,095,380WCDMA subscribers reached 114,664,827cdmaOne had 36,280,000 subscribersCDMA2000 h d 350 820 000 b ibCDMA2000 had 350,820,000 subscribers


Signals to be transmittedSignals to be transmitted

Optical fibre

Copper wire


Microwave link right choiceMicrowave link right choice

Microwave Link


The same old question.....The same old question.....The same old question.....The same old question.....

Once more: why wireless?Once more: why wireless?

........ to overcome mountains and sees........ to overcome mountains and sees

........ to get rid of cables, fibres, permissions, roads........ to get rid of cables, fibres, permissions, roads

........ to get a fast roll........ to get a fast roll--outout


Radio System EngineeringRadio System Engineeringy g gy g gA microwaves plant can be made of several items, starting from the A microwaves plant can be made of several items, starting from the p , gp , gsimple equipment delivery up to complex turnsimple equipment delivery up to complex turn--key projects, which key projects, which imply a set of computational activities:imply a set of computational activities:

EQUIPMENT + ANTENNAS + TOWERS + ENERGY + INFRASTRUCTURESEQUIPMENT + ANTENNAS + TOWERS + ENERGY + INFRASTRUCTURES

EQUIPMENT + ANTENNAS + TOWERS + ENERGYEQUIPMENT + ANTENNAS + TOWERS + ENERGY

EQUIPMENT + ANTENNAS + TOWERSEQUIPMENT + ANTENNAS + TOWERS

EQUIPMENT + ANTENNASEQUIPMENT + ANTENNAS


EQUIPMENT ONLYEQUIPMENT ONLY

What about distance & availability?What about distance & availability?

Link4 GHz ~60km7 GHz ~40km Link

availability10 GHz ~20km15 GHz ~15km23 GHz ~6km38 GHz ~3km

Hop lengthWeather and propagationconditions


Microwave Applications: Frequency vs. CapacityMicrowave Applications: Frequency vs. Capacity

Distance CapacitLong Haul Short Haul High Capacity Low Capacity4 , 4U, 6, 6U 6, 6U, 7.4, 8, 11, 13 STM - 0 16 x 2

Distance Capacity

Application

7, 8, 11GHz 15, 18, 23, 25, 28, 38GHz STM - 1 2 Mb/ s

Transport NetworksCellular NetworksISP / ASP Networks

Data NetworksPTO/ Competitive Ac. Providerp

LMDS NetworksDVBT Networks

Private Networks

ISP - Internet Service ProviderASP - Application Service ProviderPTO - Public Telecommunications Operator


pLMDS - Local Multipoint Distribution ServicesDVBT - Digital Video Broadcast Transmission

Alcatel: 9600USY_Basic ConfigurationsAlcatel: 9600USY_Basic Configurations

1+1/2+0ODU 1+0

ODU

V/H pol.ODU - Outdoor Unit

1+1/2+0IDU

1+0IDU

IDU - Indoor Unit


IDU Indoor Unit

9600USYProduct / features availability

128 QAM 128 QAM 16 QAM 16 QAM FREQ. CHANNEL

MODELBAND(GHZ)

ITU-RRec. STM-1 STM-0 STM-1 STM-0

AGILITY SEPARATION (MHZ)

9662 USY 5.9 - 6.4 F.383 YES N O N O N O N O 29.65 / 28

9667 USY 6.4 - 7.1 F.384 YES N O N O N O N O 409667 USY 6.4 7.1 F.384 YES N O N O N O N O 40

9674 USY 7.1 - 7.7 F.385 YES YES N O N O YES 14 / 28

9681 USY 7.7 - 8.3 F.386 YES YES N O N O N O 14 / 28 / 29.65

9611 USY 10 7 11 7 F 387 YES N O N O N O N O 409611 USY 10.7 - 11.7 F.387 YES N O N O N O N O 40



9618 USY 17 7 19 7 F 595 YES YES YES YES YES 13 75/ 27 5/ 559618 USY 17.7 - 19.7 F.595 YES YES YES YES YES 13.75/ 27.5/ 55

9623 USY 21.2 - 23.6 F.637 YES YES YES YES YES 14 / 28 / 56

9625 USY 24.5 - 26.5 F.748 YES YES YES YES YES 14 / 28 / 56

9628 USY 27.5 - 29.5 F.748 YES N O YES YES YES 14 / 28 / 56

9632 USY 31.8 - 33.5 F.1520 YES N O YES YES YES 14 / 28 / 56

9638 USY 37 - 40 F.749 YES N O YES YES YES 28 / 56


9400AWY Basic Configurations9400AWY Basic Configurations

1+0 Compact1 0 Compact ConfigurationWith Integrated Antenna (30 + 60cm)

Split Mount StructureInside ODUInside ODU

• Transceiver + Modem

Inside IDUInside IDU• All Base band

functionsIDU CompactIDU Compact


9400 AWY 9400 AWY Ethernet Ethernet AccessAccess

Access Ethernet/Data networks 7 / 8 G Hz ETSI

13 G Hz ETSI Access Ethernet/Data networks 15 G Hz ETSI-FCC

18 G Hz ETSI-FCC

23 G Hz ETSI-FCC

24 G Hz FCC 24 G Hz FCC

25 G Hz ETSI

28 G Hz ETSI

31 G Hz FCC

32 G Hz ETSI

38 G Hz ETSI-FCC

ExchangeExchange

ExchangeExchange


Marconi Fixed RadioMarconi Fixed RadioMarconi Fixed RadioMarconi Fixed RadioCapability, experience and suitability for Iraq Capability, experience and suitability for Iraq reconstr ctionreconstr ctionreconstructionreconstruction


Radio Radio -- OverviewOverview

The technology that forms the majority of Marconi’s The technology that forms the majority of Marconi’s sales in Central Europe and CALA sales in Central Europe and CALA A product line with a long heritage and reputationA product line with a long heritage and reputationA product line with a long heritage and reputation A product line with a long heritage and reputation traceable to traceable to GuglielmoGuglielmo MarconiMarconi

Unique R&D Capability W d i d k RF t d th i f t iWe design and make RF components and their manufacturing processesAlso design and manufacture high performance antennas

Fixed wireless applications confront a number of constraints that Marconi i li i i h i h i ifi l dd i i ispecialise in overcoming these with significant value-add activities

Performance and physical planningSite acquisition and erectionInstallation and commissioning

Marconi wireless products are robust, reliable, feature rich and well respectedp

Most customers are long-term customersNew products establish Next Generation multi-service radioFully managed product offering which covers all MW applications from


Fully managed product offering which covers all MW applications from WiMAX to SDH core radio.

Market SegmentationMarket Segmentation

SDH RadioSDH Radio•• Specialised field, relatively few playersSpecialised field, relatively few playersp , y p yp , y p y•• Long haul requires highly skilled planningLong haul requires highly skilled planning•• Market segments:Market segments:

–– Cellular high capacity backhaul (E.G. linking BSC’s)Cellular high capacity backhaul (E.G. linking BSC’s)–– Metro AccessMetro Access–– Long Haul Long Haul CoreCore


Microwave Radio Portfolio (Microwave Radio Portfolio (PtPPtP & & PmPPmP))Core Applications Metro Applications Residential SME LE Access and Backhaul ApplicationsCore Applications Metro Applications Residential, SME, LE Access and Backhaul Applications

MDMS

3.5, 3.7, 10.5,7, 13, 15, 18, 23

MDRS SH PDH AXR

3.5, 7, 8, 10, 13, 15, 18 3.5, 5.8 (FD/TDD)

AS.MaxMDRS SH SDH

7, 8, 11, 13, 15, 18,

MDRS LH SDH

4, 5, L6, U6, 7, 3.5, 3.7, 10.5,26, 28, 32 GHz

Multiservice, POTS,ISDN, NxE1, IP, ATM

, , , ,26, 28, 38 GHz

NxE1 (N < 17)10/100BaseT

, , , , , ,23, 26, 28, 32, 38 GHz

nxE1/T1(CES, IMA),IP, STM-1 ATM

, ( )GHz (others later)

IP, nxE1/T1,VoIP, WiFi AP

, , , , , ,23, 26, 28, 32, 38GHz

NxSTM-1 (N < 6)STM-4

, , , , ,8, 11, 13 GHz

NxSTM-1 (n < 20)STM-4

Link Range (LOS)up to 10 km

Link Range (LOS)up to 40 km+

Link Range (LOS)up to 40 km PtP& 10 km+ PmP

Link Range (NLOS)up to 10 km



ASR ALR AWRAXR


ASR ALR AWRAXR

PROJEKTNI ZADATAK

za izradu Glavnog projekta za izgradnju digitalnog RR sistema prenosa protokadigitalnog RR sistema prenosa protoka

4x2Mbit/s A (Telekom) – B (Telekom)




Typical Microwave Dish Towers (Negde u SRBIJI)

Sadržaj projekta

Projekat mora da sadrži:•sadržaj projekta;•sadržaj projekta;•opšta dokumenta,•projektni zadatak,•opis tehničkog rešenja,•proračun kvaliteta i neraspoloživosti veze,•tehnički opis uređaja i njegovih elemenata•električne instalacije•tehnički uslovi za izvođenje radova•tehnički uslovi za izvođenje radova•opis montažnih radova•specifikaciju opreme i montažnog materijala,•specifikaciju montažnih radova,•specifikaciju umeravanja i puštanja RR sistema u rad (kontrola kvaliteta),•rekapitulacija troškova,•organizacija radova,•mere zaštite od požara bezbedonosne mere na radu i mere zaštite životne sredine•mere zaštite od požara, bezbedonosne mere na radu i mere zaštite životne sredine,•listu standarda, propisa i preporuka,•pregled posebnih podataka (priloge),•grafička dokumentacija (crteži).


Introduction to Computer Aided Circuit Design The steady growth in commercial interest in RF,microwave and millimetre wave systems, especially in

i l i i i d li iwireless communications, security and sensor applications,and military and transportation electronics, has provided a significant challenge to conventional microwave circuitssignificant challenge to conventional microwave circuitsand their design methodologies. Recent advances in RF,microwave and millimetre-wave computer-aided circuitmicrowave and millimetre wave computer aided circuit design technology suggest the feasibility of interfacingelectromagnetic simulations directly to sophisticatedg y poptimization systems.


With the availability of powerful computers andworkstations this optimization based approach to the designof microwave circuits becomes a desirable tool. CAD has become an essential tool in the design and manufacturingbecome an essential tool in the design and manufacturingof RF, microwave and mm-wave circuits and systems.

Why CAD?

Computer Aided Design of RF, microwave and millimetre-wave circuit structures must be developed to account for all pthe theoretical and practical effects present, and thereby enable company to provide rapid delivery times at low t h i l i k Fl h t f i it d i i h itechnical risk. Flow chart for circuit design is shown in Figure below.


CIRCUIT SPECIFICATIONS

ARE CIRCUIT DIMENSIONS KNOWN ?

SYNTHESISSYNTHESIS

EM SOLVERSHFSS (3D-FEM)

MICROSTRIPE (3D-TLM)

OPTIMIZER

MICROSTRIPE (3D-TLM)SONNET (2.5D-MoM)EMSIGHT (2.5D-MoM)

EMPIRE (3D-FDTD)WIPL (3D-MoM)

OPTIMIZER

ARE SPEC'S MET ?

(EROPTIM)

ARE SPEC S MET ?

FABRICATION

YESNO


FABRICATION

C t Aid d D i f RF i dComputer Aided Design of RF, microwave andmillimetre-wave circuits must be capable ofhandling the restrictions of a wide spreadhandling the restrictions of a wide-spreadapplication of low-cost precision fabricationmethods, such as computer-controlling milling,methods, such as computer controlling milling,spark eroding or photo-lithographic etchingtechniques, in which postassembly tuning is noq p y glonger economical or feasible. The circuit designmust also meet the demands of the expandingutilization of higher frequency bands (up tosubmm-waves), which need tighter tolerances.Th diti iThese conditions require


• Computer aided analysis,

• Rigorous electromagnetic simulation techniques

* Efficient computer optimization methods

that allow the computer aided filter design to take intoaccount all of the significant design parameters


Simulation software packages (see Table below) providedifferent methods for optimization of circuit elements.Th h d f l li i d dThese methods are for general applications and do notprovide the results that are required in the specific area ofRF microwave mm wave and submm wave circuitsRF, microwave, mm-wave and submm-wave circuits.Usually the response of an optimizable circuit is sampled ata number of equally spaced frequencies and the errora number of equally spaced frequencies and the errorbetween this sampled response and the desired response iscomputed at each frequencyp q y


Some Commercially Available Circuit and Some Commercially Available Circuit and System Design ToolsSystem Design ToolsFrom the large amount of software packages the modern requirements of th WBA d i f lfill d b th ft fthe WBA design are fulfilled by the software of :

Commercial circuit simulatorsOriginator Packageg gAgilent-Eesof ADSAWR Microwave officeAnsoft DesignerCST D i St di (DS)CST Design Studio (DS)

Comercial electromagnetic simulatorsAnsoft HFSSAgilent MomentumAWR em simulatorSonnet emZeland IE3DZeland IE3DFlomerecs MicroStripesCST Microwave studio (MWS)IMST


MICIAN

Some Commercially Available Circuit Design, Electromagnetic Simulators and System Design Tools. COMPANY PRODUCT

(all trademarksTYPE

(all trademarks acknowledged)

AGILENT Technologies www.tm.agilent.com/

ADS (Advanced Design System)

Integrated package: Linear Simulator Harmonic balance, Time-domain Integrated package: Integrated frameworkwww.tm.agilent.com/

eesof

Integrated package: Integrated framework that combines the previous Series IV and MDS suites with DSP and communications system design modules)

Momentum

3D Planar electromagnetic simulater

ANSOFT HFSS FEM-3D Arbitrary electromagnetic simulator www.ansoft.com

MAXWELL SV

2D electromagnetic simulator

DESIGNER SV

Integrated package: linear simulator,harmonic balance, time-domain and communications system design


COMPANY PRODUCT(all trademarks acknowledged)

TYPE

APPLIED WAVE RESEARCH (AWR)

Microwave Office Linear and non-linear circuit and system i l tRESEARCH (AWR)

www.mwoffice.com EM Sight VSS (Visual

simulator 3D electromagnetic Design of complete communication systems:VSS (Visual

System Simulator)Design of complete communication systems:RF budget analysis

FLOMERICS Micro-Stripes TLM 3-D Arbitrary electromagnetic analysis for antenna and microwave design.

Sonnet Software

em

3-D Planar electromagnetic

Computer System Technologies (CST)

Microwave Studio 3D Arbitrary electromagnetic

www.cst.de ZELAND Software Inc. IE3D

Fidelity

Planar & 3D electromagnetic simulation and optimization Time Domain FDTD Full 3D electromagneticFidelity Time-Domain FDTD Full-3D electromagneticsimulation

BERNARD MICROSYSTEMS

Wavemaker MMIC Layout, schematic capture


MICROSYSTEMS

Waveguide FiltersAN APPROXIMATE SYNTHESIS-BASEDPROCEDURE FOR THE DESIGN OF DIRECT-COUPLED CAVITY FILTERS

The design procedure which will be outlined below is basedThe design procedure, which will be outlined below, is basedon a formulation proposed by Rhodes for an optimumChebyshev distributed stepped impedance low pass prototype.y pp p p p ypIt is a distributed filter (Figure 1a) consisting of a cascade of nline elements (unit elements); each element corresponds to a

t i th ti l filt d i Th l tresonator in the conventional filter design. The elements,having characteristic impedances Zr (r=1,2,...,n) are assumed tohave an equal length of λgo/2, where λgo is the guide wavelengthhave an equal length of λgo/2, where λgo is the guide wavelengthof the line at the centre frequency. The electrical response ofthis transmission line structure depends upon the impedances of


the unit elements.

F l i i l h li hFor electromagnetic waves propagating along the line, theimpedance differences between the unit elements yield reflectedwaves which after appropriate arrangement will cancel eachwaves which, after appropriate arrangement, will cancel eachother at the desired frequencies. However, if a uniformwaveguide is used to implement the circuit, all the unitelements are of the same impedance; the necessary wavereflections must be produced by inserting some sort ofdiscontinuities between the unit elements For a cascade of unitdiscontinuities between the unit elements. For a cascade of unitelements (Figure 1a), an optimum equal ripple bandpassresponse occurs around θ=π whenp θ π


) (T2n2+11 = |2S12|

θαε sin(6.4)

where

)(Tnε

λλπθ g0= (6 5)

and

λθ g (6.5)

1|>|f)1-(( ) h 1|>x| for ) x1-n(=(x)Tn coshcosh (6.6)

1x<0 for ) x1- n ( = (x)Tn ≤coscos (6.7)


is the nth degree Chebyshev polynomial of the first kind. a definesthe passband bandwidth (scaling parameter), ε defines thep ( g p ), εpassband ripple level, λgo is the guide wavelength at the centrefrequency, and λg is the guide wavelength. In the abovediscussion the discontinuities are assumed to be frequencydiscussion, the discontinuities are assumed to be frequencyindependent. This is hardly true in practice. The frequencydependent behaviour of the discontinuity has significant effectson the filter performance In an earlier paper Levy has studied inon the filter performance. In an earlier paper Levy has studied indetail the reactance coupled filters and concluded that the responsein (6.4) should be modified as

⎟⎟⎟

⎠

⎞

⎜⎜⎜

⎝

⎛

⎟⎟⎟

⎠

⎞

⎜⎜⎜

⎝

⎛

λλπ

λλαε g

g0 g0g T2n 2 + 1

1 = |2S12|sin

(6.8)

⎠⎝ ⎠⎝


to take into account the linear frequency dependence of thediscontinuities.T d i filt i ll i th t b d dTo design a filter one is normally given the two passband edgefrequencies yielding λg1 and λg2 , passband return loss (LR), stop bandattenuation (LI), the waveguide housing dimensions (a,b) and the metalseptum thickness (t) . The design procedure is as follows:

(1) From λg1 and λg2 one can determine the parameters α and λgo from( ) g g p g

the following nonlinear equations which can be readily solvednumerically:

gog1 ⎟⎞

⎜⎛ λπλα

1=g1

gogog1

⎟⎟⎟

⎠

⎞

⎜⎜⎜

⎝

⎛

λλπ

λλα sin

(6.9)

1- = g2go go

g2⎟⎟⎟

⎠

⎞

⎜⎜⎜

⎝

⎛

λλπ

λλα sin


where λg2 and λg1 are the guide wavelengths at theg g g gupper and lower bandedge frequencies respectively.Equation (6.9) comes from the property of theChebyshev polynomial of the first kind whichChebyshev polynomial of the first kind whichoscillates between +1 and -1. Adding the two parts ofequation (6.9) gives

0201 ⎞⎛⎞⎛ λπλαλπλα

If λ λ λ then we may approximate (6 10) as

. 0 = g2g0 )f 2(

g2 + g1g0 )f 1(

g1⎟⎟⎟

⎠

⎞

⎜⎜⎜

⎝

⎛

⎟⎟⎟

⎠

⎞

⎜⎜⎜

⎝

⎛

ΔΔ λλπλα

λλπλα sinsin (6.1

If λg1 ≈ λg2 ≈ λgo then we may approximate (6.10) as

0 = g2g0-1 )f 2(

g2 + g1g0-1 )f 1(

g1⎟⎟⎟

⎠

⎞

⎜⎜⎜

⎝

⎛

⎟⎟⎟

⎠

⎞

⎜⎜⎜

⎝

⎛

ΔΔ λλπλα

λλπλα

(6.11)


givinggo

g1 g2 = +

2 .λ

λ λ

(6.12)

However, for broad bandwidths this will not be sufficientlyaccurate and a better solution is obtained by applying the Newton-Raphson technique as follows. Letp q

*go g1

go

g1g2

go

g2F ( ) = + .λ λ

π λλ

λπ λλ

sin sin⎛

⎝⎜⎜

⎞

⎠⎟⎟

⎛

⎝⎜⎜

⎞

⎠⎟⎟

(6.13)

Then differentiating w.r.t. λgo gives


. + = )(F*g2

gog2

g1

gog1go ⎟

⎟

⎠

⎞

⎜⎜

⎝

⎛

⎟⎟

⎠

⎞

⎜⎜

⎝

⎛

λλπλλ

λπλλ sinsin (6.14)gg ⎠⎝⎠⎝

and the modified value of λgo will be

.)(F*-=new goλλλ ′ (6 15).

)(F go

g1go

λλλ ′ (6.15)


(2) Determine the passband ripple level from the minimumpassband return loss which is defined as:

⎟⎟⎟⎞

⎜⎜⎜⎛

21+11010=LR log (6.16)

(3) Determine the number of resonators n from (6.17). This is

⎟⎠

⎜⎝ ε210LR g ( )

accomplished by finding the minimum value of n for whichthe most severe constraint on the stop band insertion loss level(L ) satisfies(LI) satisfies

⎥⎥⎥

⎦

⎤

⎢⎢⎢

⎣

⎡

⎟⎟⎟

⎠

⎞

⎜⎜⎜

⎝

⎛

⎟⎟⎟

⎠

⎞

⎜⎜⎜

⎝

⎛

gg0

g0g T 2n 2 + 1 10 10 = LI λ

λπλλαε sinLog

at the designated stop band frequency f In (6 17) λ is the

⎦⎣ ⎠⎝ ⎠⎝ gg

(6.17)

at the designated stop band frequency fs. In (6.17) λg is theguide wavelength at fs.


(4) For a cascade of unit elements with the( ) o c sc de o u e e e s w etransfer characteristic given by (6.4) one maysynthesise the network to obtain theh t i ti i d f th it l tcharacteristic impedances of the unit elements.

However, for up to moderate bandwidths onemay use explicit formulas for the elementmay use explicit formulas for the elementvalues. Modifying the network by introducingimpedance inverters of the characteristici d K h i Fi 1b himpedances Kr,r+1 as shown in Figure 1b, theexplicit formulas for the impedance values are


where

⎟⎟⎟⎞

⎜⎜⎜⎛

⎟⎟⎞

⎜⎜⎛

′)n

r( 2 + y21- ) 1 - 2r (2=Zrππα sinsin

⎟⎟⎟⎟

⎠⎜⎜⎜⎜

⎝

⎟⎟⎠

⎜⎜⎝

2n)1+2r( y4-2nyZr πα sin

sin

n1,2,....,=r ,

2) 3 - 2r (n

) 1 - r ( 2 + y2 y4

1 -⎟⎟⎟⎟⎟⎟⎞

⎜⎜⎜⎜⎜⎜⎛

π

π

α sinsin

2n ⎟⎠

⎜⎝

with

n0,1,....,=r ,y)n

n( 2 + y2 = K 1+r,r

πsin′ y

(6.19)


(5) In the rectangular waveguide realization, sincethe waveguide is uniform we must scale the internalthe waveguide is uniform, we must scale the internalimpedance level as shown in Figure 1c where

0,1,...n=r , Z Z

K = Krr

1+r,r1+rr,

1//

+

′ (6.21)

with1. = Z= Z nn 1

//+ (6.22)


(6) Determine the ith septum length di by solving equation(6 3) so that the required impedance inverter is realized The(6.3) so that the required impedance inverter is realized. Thenormalized reactances xa and xb are a function of the septumwidth as mentioned before in previous section. Since thesefunctions are not available explicitly, we must implement aroot-seeking routine to find the value of width that is

id d b th i d i d l K d th l fprovided by the required impedance value K and the angle ffor each impedance inverter.


(7) Finally, the length of the ith resonator (li) formed by ithand (i+1)th septa is given byand (i+1)th septa is given by

( ) ⎤⎡ 1goλ (6 23)( )⎥⎥

⎦

⎤

⎢⎢

⎣

⎡ 1+i+i21-2

go=li φφππλ (6.23)

where fi is given by (6.1), and the electrical distance πcorresponds to the physical distance λ /2corresponds to the physical distance λgo/2.


Calculation of insertion loss and return loss

In order to design E-plane filters for a given set of metalinsert dimensions using the equal ripple optimizationinsert dimensions using the equal ripple optimizationmethod described in reference, it is necessary to be ableto calculate the insertion loss on a sample of frequencypoints within the specified passband. In the case oflongitudinally symmetrical structures such asconventional E plane bandpass filters the insertion lossconventional E-plane bandpass filters the insertion loss(LI) can be expressed in terms of normalized even andodd mode impedances asp


)z+(1)z+(120=L oeLog (6 36a)

where jze(o) is the normalised input impedance of the two

z-z)()(20=L

oe10I Log (6.36a)

identical one-ports formed by placing a magnetic(electric) wall at the plane of symmetry. By transformingan open (short) circuit placed at the plane of symmetryan open (short) circuit placed at the plane of symmetrythrough the filter sections (resonators and E-plane septa)located to the left of the plane of symmetry, ze(o) can bep y y ( )calculated. Each E-plane septum is itself symmetrical andcan be electrically represented by normalised even anddd d i dodd mode impedances


)x2+xj( = z pisiei (6.36b)

(6 36 )

For a normalised reactive impedance jz an E-planef h li d i d

. xj=z sioi (6.36c)

septum performs the normalised impedancetransformation jz ⇒ jzin where zin is given by

2+)+( . )z+z(+2zzz2+)z+zz( = z

oiei

oieioieiin

(6.36d)


A t ti i l th f id f thA resonator section, i.e. a length of guide, performs thenormalised impedance transformation jz ⇒ jzin where zin isgiven bygiven by

lz - 1l +z = zin ββ

tantan

h β ( 2 /λ ) i th ti t t d l i th

(6.36e)

where β ( = 2π/λg) is the propagation constant and l is thelength of the resonator. By applying (6.36d) and (6.36e) itis possible to calculate ze and zo starting at the centre of theis possible to calculate ze and zo starting at the centre of thefilter and working outwards. This process involves nomatrix manipulation and uses only real arithmetic. For theanalysis of E-plane septa in a rectangular waveguide, themode-matching method was used.


Example 37

Waveguide bandpass filter (see Figure below) with the following specifications is considered.

Waveguide WG16 (WR90):Internal dimension 22.86 x 10.16 mmMidband frequency: 9.75 GHzPassband: 9.50-10.00 GHzRipple level: 0.05 dBPassband return loss: 20 dB minStopband Insertion loss at Fsb: 70dBStopband frequency (Fsb): 10.5GHzFilter characteristic: ChebyshevFind number of resonators (filter degree).( g )


i iExample: Waveguide Filter

Ideal requirement to pass signals with no loss in theIdeal requirement to pass signals with no loss in thefrequency band 27.5 - 28.5 GHz

• Type: Bandpass• Passband: 27.5 - 28.5 GHz

P b d fl t b tt th 0 2dB• Passband flatness better than 0.2dB• Passband insertion loss <0.5dB (smaller if possible)• Passband return loss >20dB• Passband return loss >20dB• Rejection at 30.0 GHz >45 dB


100.00Insertion loss (dB)

80.00Return loss (dB)

60.00

40.00

0 00

20.00

25.00 26.00 27.00 28.00 29.00 30.000.00

Frequency (GHz)Frequency (GHz)

Calculated insertion loss (solid line) and return loss (dashed line)


Calculated insertion loss (solid line) and return loss (dashed line)of the E-plane bandpass filter at 28 GHz.

Laboratory: Lab1.Time Allowed: 120 minTime Allowed: 120 min.

Room: NLG105Project Title: Passive Bandpass Filters


DJB_EPFIL:

The EPFIL software is currently used by more than 1000 y ycompanies and universities all over the world.


100.00

B)

80.00

Los

s (dB

)Measurement

Theory

60.00

ertio

n L

40.00Inse

20.00

8.00 9.00 10.00 11.00 12.00 13.000.00

Frequency (GHz)Frequency (GHz)

Measured insertion loss (dashed line) and calculated


insertion loss (solid line) of the E-plane filter by DBFILTER.

50.00

40.00(dB

)

30.00

rn L

oss

20.00Ret

ur

10.00

0.009.20 9.60 10.00

Frequency (GHz)

D. Budimir; Westminster University LondonMeasured return loss of the E-plane bandpass filter

WCRG Wireless Communications

Facilities

WCRG Wireless CommunicationsResearch Group

Facilities

Measurement Facilities (Test Equipment)( q p )

Agilent E8361A 67GHz Vector Network Analyzer for testing components for wireless and mobile communications.components for wireless and mobile communications.

Photograph of the waveguide E-plane filter for LMDS


Photograph of the waveguide E plane filter for LMDS.

Digital Radio Transceiver Digital Radio Transceiver ggTransceiver Front End

Up and down conversion of signalUp and down conversion of signal.Power amplification and filtering before transmission. Filtering and power amplification by keeping noise level g y gand distortion minimum on receiving side.


IntroductionIntroductionMicrowave digital radio transceivers are key componentsMicrowave digital radio transceivers are key components

IntroductionIntroductionMicrowave digital radio transceivers are key components Microwave digital radio transceivers are key components in modern wireless systems. in modern wireless systems.

Transceiver consist of Digital baseband processor, IF Transceiver consist of Digital baseband processor, IF section , RF section and Antenna.section , RF section and Antenna.

Waveguide Waveguide bandbassbandbass filters suppresses unwanted filters suppresses unwanted signals in RX and TX bands and pass required onessignals in RX and TX bands and pass required onessignals in RX and TX bands and pass required ones.signals in RX and TX bands and pass required ones.

The projects presents design of EThe projects presents design of E--plane rectangularplane rectangularThe projects presents design of EThe projects presents design of E plane rectangular plane rectangular waveguide waveguide bandpassbandpass filtersfilters in 18GHz band and in 18GHz band and implementing them in transceiver.implementing them in transceiver.


Block Diagram of the Front-End of Typical Microwave Digital Radio:


Radio Frequency Bands


Digital Radio Transceiver Digital Radio Transceiver Transceiver Design issues

IMD and spurious emission – Keep 1dB compression d Thi d d i t t i t l l f PAand Third order intercept point power levels of PA

within its range.

System gain – affect link budget and affect receiver stability.

Receiver sensitivity and dynamic range.

Selectivity of receiver- rejects adjacent signal frequencies, images and interference.

Noise figure – measure how SNR is distorted by noise ; LNA need small NF and high gain.


LNA need small NF and high gain.

WaveguidesWaveguidesMetallic pipes which direct electromagnetic waves in particular direction by containing the energy; supports TE and TM modesand TM modes.

+ Higher power handling capacity, low manufacturing cost and low loss per unit length.

– Large cross section dimensions.

T d d ti d fi tiTypes depend on cross section and configuration Rectangular waveguide –widely used and most common.Ci l W id H d l l i ti bilitCircular Waveguide – Have dual polarization capability.Rigid waveguide – RW with merit of increased bandwidth and reduced size but have higher lossand reduced size but have higher loss.Other types include dielectric loaded, fin-line and coplanar waveguide


coplanar waveguide.

Electromagnetic Modelling of BPFElectromagnetic Modelling of BPFPerformed by analysing electromagnetic waves in Performed by analysing electromagnetic waves in waveguide using Maxwell equations.waveguide using Maxwell equations.g g qg g qAnalysing electromagnetic behaviours of discontinuities in Analysing electromagnetic behaviours of discontinuities in waveguide waveguide –– inductive strips in Einductive strips in E--plane rectangular plane rectangular gg pp p gp gwaveguide.waveguide.Using mode matching method to characterise E and H Using mode matching method to characterise E and H g gg gfields (reflected and transmitted).fields (reflected and transmitted).Normalized even and odd reactive impedances areNormalized even and odd reactive impedances areNormalized even and odd reactive impedances are Normalized even and odd reactive impedances are obtained from reflection coefficients. obtained from reflection coefficients. SS--Parameters are then obtained from normalized even andParameters are then obtained from normalized even andSS Parameters are then obtained from normalized even and Parameters are then obtained from normalized even and reactive impedances, which then can be used to calculate reactive impedances, which then can be used to calculate the series and parallel reactive impedances for a septum the series and parallel reactive impedances for a septum


p p pp p pelectrical representation. electrical representation.

Electromagnetic Modelling of BPFElectromagnetic Modelling of BPF


Waveguide Waveguide BandpassBandpass Filter DesignFilter Design

Waveguide EWaveguide E--plane all metal inserts BPFs were designed plane all metal inserts BPFs were designed with following specificationswith following specificationswith following specifications with following specifications

Receiver BPF Transmitter BPF

Parameter Value (unit) Parameter Value (unit)

Lower Frequency 18.07 GHz Lower Frequency 18.485 GHz

≥≥

Upper Frequency 18.17 GHz Upper Frequency 18.585 GHz

Passband Return loss 20 dB Passband Return loss 20 dB

≥ ≥

≤ ≤

Highband Rejectionat 8.4GHz

60 dB Lowband rejectionat 18.3GHz

60 dB

Passband Ripple Level 0 05dB Passband Ripple Level 0 05dB≤ ≤Passband Ripple Level 0.05dB Passband Ripple Level 0.05dB

Metal insert thickness 0.1 mm Metal insert thickness 0.1 mm

Characteristic Chebyshev


Characteristic Chebyshev

Waveguide Waveguide BandpassBandpass Filter DesignFilter DesignSteps in designing the waveguide Steps in designing the waveguide bandpassbandpass filter (Efilter (E--Plane)Plane)-- Determining number of Determining number of Resonators requiredResonators required

W id di i d t i tiW id di i d t i ti di i ff t th tdi i ff t th t ff fff fWaveguide dimensions determination Waveguide dimensions determination –– dimension affect the cutdimension affect the cut--off frequency , off frequency , hence the operating band; usable rangehence the operating band; usable range

Dimension for both BPF : Dimension for both BPF : a = 12.954mm a = 12.954mm andand b=6.477mmb=6.477mm , WR51, WR51

Determining the centre frequency : using and , then corresponding guide Determining the centre frequency : using and , then corresponding guide wavelengths atwavelengths at

cff c 1.9to25.1

f Lf Hfwavelengths atwavelengths at

Determining scaling parameter, from Determining scaling parameter, from DeterminingDetermining passbandpassband ripple level from given minimumripple level from given minimum passbandpassband return lossreturn loss

of Lf HfSHL ffff , , ,0

Determining Determining passbandpassband ripple level , from given minimum ripple level , from given minimum passbandpassband return loss. return loss.


⎥⎤

⎢⎡

⎟⎞

⎜⎛

⎟⎞

⎜⎛22110 g0g λπλα

iL⎥⎥⎦⎢

⎢⎣

⎟⎟⎠

⎜⎜⎝

⎟⎟⎠

⎜⎜⎝

T 2n2+110 = Lg

g0

g0

g10I

λλ

λλ

ε sinLog

⎞⎛⎟⎟⎠

⎞⎜⎜⎝

⎛

ε21 + 1 10 = L 10R log

( )⎥⎦⎤

⎢⎣⎡ − xn = xnT 1coshcosh)(

⎤⎡ 1

,for ⎢x|⎢>1 and

( )⎥⎦⎤

⎢⎣⎡ − xn = xnT 1coscos)(

⎞⎛

, for 0<|x|≤1

1sin 0

0⎟⎟⎠

⎞⎜⎜⎝

⎛ =

gL

g

g

gL

λλπ

λλα

1sin 0

0−⎟

⎟⎠

⎞⎜⎜⎝

⎛ =

gH

g

g

gH

λλπ

λλα


⎠⎝

Waveguide Waveguide BandpassBandpass Filter DesignFilter DesignNumber of resonators, is determined by analysing the insertion loss, to satisfy Number of resonators, is determined by analysing the insertion loss, to satisfy the minimum rejection at .the minimum rejection at .Sf

))(1log(10)(22

xTdBL nI ε+=

1S ⎟⎞

⎜⎛ λαλ

Th b f t i d t i d 5Th b f t i d t i d 5

)coshcosh()(sin10

0xnxTx n

gS

g

g

gS −=⎟

⎟⎠

⎞⎜⎜⎝

⎛= K

λπλ

λαλ

The number of resonators is determined = 5.The number of resonators is determined = 5.The resonator lengths are calculated by considering the characteristic The resonator lengths are calculated by considering the characteristic impedance (Zimpedance (Z--values) and impedance inverters (Kvalues) and impedance inverters (K--values) and then values) and then corresponding electrical lengths are calculated.corresponding electrical lengths are calculated.Using electrical lengths, physical lengths can be determined assuming Using electrical lengths, physical lengths can be determined assuming is equivalent to is equivalent to

20gλ


Waveguide Bandpass Filter Design

f gλf gλReceiver Transmitter

Frequency (GHz)

Guide wavelength (mm)

Frequency (GHz)

Guide wavelength (mm)

Lf gLλLf gLλ

Hf gHλHf gHλ

f λf λ

(GHz) wavelength (mm) (GHz) wavelength (mm)

18.07 21.6258 18.485 20.8207

18.17 21.4250 18.585 20.6373Sf gSλSf gSλ

0f 0gλ0f 0gλ

18.40 20.9797 18.300 21.1706

18.12 21.5254 18.535 20.7290

αα

xx

Parameter Value Parameter Value

68.2491 71.9458

5.4294 4.8114

)(xTn )(dBLI)(xTn )(dBLIValue of n Value of n

1 5.4294 1.1319 1 4.8114 0.91261 5.4294 1.1319 1 4.8114 0.9126

2 57.9564 15.4318 2 45.2991 13.3701

3 623.9052 35.9471 3 431.0927 32.7374

4 6716 8834 56 5870 4 4103 0188 52 3057


4 6716.8834 56.5870 4 4103.0188 52.3057

5 77313.1471 77.2280 5 39051.4240 71.8764

Waveguide Waveguide BandpassBandpass Filter DesignFilter DesignReceiver Transmitter

Z-Parameter Value K-Inverter Value Z-Parameter Value K-Inverter Value0Z 6Z

5601 KK =0Z 6Z 5601 KK =

1Z 5Z 4512 KK = 1Z 5Z4512 KK =

2Z 4Z 3423 KK =2Z 4Z 3423 KK =

= 1.00 1.0000 = 1.0000 1.0000

= 66.30 1.3614 = 69.8927 1.3614

= 173.54 1.7984 = 182.9488 1.79842Z 4Z

3Z3Z173.54 1.7984 182.9488 1.7984

214.52 226.1409

B parameter Value Electrical Value B parameter Value Electrical Value

5601 BB = 51 θθ =5601 BB = 51 θθ =

4512 BB =42 θθ =4512 BB = 42 θθ =

B-parameter Value Electricallengths

Value(rad)

B-parameter Value Electricallengths

Value(rad)

8.0197 3.0067 8.2406 3.0105

78 7773 3 1196 83 0485 3 12074512424512 42

3423 BB =3θ3423 BB = 3θ

78.7773 3.1196 83.0485 3.1207

107.2778 3.1230 113.0926 3.1239

R t L th V l ( ) R t L th V l ( )

51 rr LL =51 rr LL =

42 rr LL =42 rr LL =

Resonator Length Value (mm) Resonator Length Value (mm)

7.107 6.853

7.374 7.104


3rL3rL 7.382 7.111

Waveguide Waveguide BandpassBandpass Filter DesignFilter DesignMetal septa lengths are calculated on given ranges of guide Metal septa lengths are calculated on given ranges of guide wavelengths for initial simulation and iteratively changed till required wavelengths for initial simulation and iteratively changed till required response is obtainedresponse is obtainedresponse is obtained.response is obtained.Receiver BPF Simulation ResultsReceiver BPF Simulation Results


Waveguide Waveguide BandpassBandpass Filter DesignFilter Design

Transmitter BPF Simulation ResultsTransmitter BPF Simulation ResultsIn both filters; minimum In both filters; minimum passbandpassband return loss (>20dB), rejection at return loss (>20dB), rejection at stopbandstopband freq enc (>77dB) band idth (100MH ) andfreq enc (>77dB) band idth (100MH ) and passbandpassbandstopbandstopband frequency(>77dB), bandwidth (100MHz) and frequency(>77dB), bandwidth (100MHz) and passbandpassbandripple level <0.05dB. ripple level <0.05dB.


Waveguide Waveguide BandpassBandpass Filter DesignFilter DesignFinal resonator and metal septa lengths are summarized belowFinal resonator and metal septa lengths are summarized below

Receiver TransmitterResonator Value (mm) Resonator Value (mm)

51 rr LL = 51 rr LL =

LL LL

length length7.46515 7.022427 46840 7 0218842 rr LL = 42 rr LL =

3rL3rL

7.46840 7.021887.46855 7.02188

LL =

Metal septumlength

Value (mm) Metal septumlength

Value (mm)

4 489 4 745761 mm LL =61 mm LL =

52 mm LL =52 mm LL =

43 mm LL =43 LL =

4.489 4.745711.824 12.371512.834 13.4320


43 mm LL

Diplexer DesignDiplexer Design

Designed using ADS comprising filters and power divider Designed using ADS comprising filters and power divider using library components and designed DJB EFFILusing library components and designed DJB EFFILusing library components and designed DJB_EFFIL using library components and designed DJB_EFFIL BPFs.BPFs.


Diplexer DesignDiplexer DesignSimulation results for circuit with ADS filters.Simulation results for circuit with ADS filters.HighbandHighband rejection : 71.85dB and rejection : 71.85dB and lowbandlowband rejection: 64.88db with rejection: 64.88db with passbandpassband return loss : 26.4 dB and ripple level in return loss : 26.4 dB and ripple level in passbandpassband is less is less pp pppp ppthan 0.05dB.than 0.05dB.


Diplexer DesignDiplexer DesignTo simulate designed BPFs ,files converted to s2pTo simulate designed BPFs ,files converted to s2p-- file and circuit set file and circuit set as shown.as shown.


Diplexer DesignDiplexer DesignSimulation ResultsSimulation ResultsRejection at Rejection at stopbandstopband frequencies is more than 77dB with frequencies is more than 77dB with passbandpassband

t l th 20dB i h b dt l th 20dB i h b dreturn loss more than 20dB in each band.return loss more than 20dB in each band.


Transceiver DesignTransceiver DesignSystem specifications:System specifications:

TX Frequency Band 18 485 ~ 18 585 GHzTX Frequency Band 18.485 ~ 18.585 GHzRX Frequency Band 18.070 ~ 18.170 GHzTX Output Power >22 dBmRX Input Noise Figure <5dB

IF frequency (TX & RX) 4.1 GHzRF Output Return Loss >20dBRF Input Return Loss >20dBTX I t D i 22dB t 18dBTX Input Dynamic range -22dBm to -18dBmRX RF Input Range -80dBm to -30dBmTX Harmonics & Spurious <-70dBm within output carrierpemission at RF Output

pfrequency

TX RF Output IP3 > 35dBmW id I f WR 51


Waveguide Interface WR 51

Transceiver Design Transceiver Design -- TransmitterTransmitterTransmitter Schematic for LSSP simulation : power Variation, 1 dB Transmitter Schematic for LSSP simulation : power Variation, 1 dB compression gain and system gain. compression gain and system gain. p g y gp g y g


Transceiver Design Transceiver Design -- TransmitterTransmitterLSSP simulation ResultsLSSP simulation Results


10

Transceiver Design Transceiver Design -- TransmitterTransmitterHarmonic balance simulation Harmonic balance simulation –– to analyse IMD and spurious emission to analyse IMD and spurious emission


Transceiver Design Transceiver Design -- TransmitterTransmitterHB Simulation ResultsHB Simulation ResultsIMD power levels less thanIMD power levels less than 100dBm which is desirable100dBm which is desirable

gg

IMD power levels less than IMD power levels less than --100dBm, which is desirable.100dBm, which is desirable.


Transceiver Design Transceiver Design -- TransmitterTransmitterSS--Parameter simulation Parameter simulation –– system gain and return loss.system gain and return loss.In circuit source and load are terminated with 50 In circuit source and load are terminated with 50 ΩΩFiltering performance is good; waveguide BPFFiltering performance is good; waveguide BPF


Transceiver Design Transceiver Design -- ReceiverReceiver

Receiver Schematic for LSSP simulationReceiver Schematic for LSSP simulation



Receiver LSSP Simulation ResultsReceiver LSSP Simulation Results



Noise figure and System GainNoise figure and System Gain


Transceiver Design Transceiver Design -- ReceiverReceiverSS--Parameter SimulationParameter Simulation

gg


d. budimir; westminster university...

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