chapter 3 two major topics of this chapter: chapter 3 discrete-time...
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Chapter 3
Discrete-Time Fourier Transform (DTFT)
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Chapter 3
Two major topics of this chapter: Discrete-Time Fourier Transform
Discrete-Time Fourier Transform (DTFT) Basic Properties & Symmetry Relation DTFT Theorems
Discrete-Time Signals and Systems in Frequency Domain
Spectrum Analysis Frequency Response of an LTI Discrete-Time System Phase and Group Delay The Unwrapped Function
Chapter 3B
Discrete-Time Signals and Systems in Frequency Domain
4
Part B: DTFT Analysis
1. Spectrum Analysis1.1 Energy Density Spectrum1.2 Band-limited Discrete-Time Signals
2. The Unwrapped Function3. The Frequency Response of an LTI Discrete-time
System4. Phase and Group Delay
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1.1 Energy Density Spectrum
The total energy of a finite-energy sequence g[n] is given by
From Parseval’s relation we observe that
2[ ]gn
g n
22 1[ ]2
jg
ng n G e d
6
1.1 Energy Density Spectrum
The quantity
is called the energy density spectrum
The area under this curve in the range divided by is the energy of the sequence
2j jggS e G e
2
7
1.1 Energy Density Spectrum
Recall that the auto-correlation sequence rgg[l]of g[n] can be expressed as
As we know that the DTFT of g[- l] is G(e-jω), therefore, the DTFT of is given by |G(ejω)|2, where we have used the fact that for areal sequence g[n], G(e-jω)=G*(ejω)
[ ] [ ] [ ( )] [ ] [ ]ggn
r l g n g l n g l g l
[ ] [ ]g l g l
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1.1 Energy Density Spectrum
As a result, the energy density spectrum Sgg(ejω) of a real sequence g[n] can be computed by taking the DTFT of its auto-correlation sequence rgg(l), i.e.,
[ ]j j lgg gg
l
S e r l e
Wiener-Khinchin theorem
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1.1 Energy Density Spectrum
Example Compute the energy of the sequence
Here
where
sin[ ] ,c
LPn
h n nn
22
-
1[ ]2
jLP LP
nh n H e d
1, 00,
cjLP
c
H e
10
1.1 Energy Density Spectrum
Therefore, Compute the energy of the sequence
Hence, hLP(n) is a finite-energy sequence
2
-
1( )2
c
c
cLP
n
h n d
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1.2 Band-limited Discrete-Time Signals
Discrete-time signal is a periodic function of ω with a period 2π.
A full-band, finite-energy, discrete-time signal has a spectrum occupying the whole frequency range −π ≤ ω < π
A band-limited discrete-time signal has a spectrum that is limited to a portion of the frequency range −π ≤ ω < π
12
1.2 Band-limited Discrete-Time Signals
An ideal band-limited signal has a spectrum that is zero outside a finite frequency range ω 0≤ ωa≤| ω|≤ ωb ≤ π , that is
However, an ideal band-limited signal cannot be generated in practice (Why?)
0, 0( )
0,aj
b
X e
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1.2 Band-limited Discrete-Time Signals
Band-limited signals are classified according to the frequency range where most of the signal’s energy is concentrated
A lowpass, discrete-time signal has a spectrum occupying the frequency range
-π < -ωp ≤ |ω|≤ ωp<πwhere ωp is called the bandwidth of the signal
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1.2 Band-limited Discrete-Time Signals
A highpass, discrete-time signal has a spectrum occupying the frequency range ωp ≤ |ω|<πwhere the bandwidth of the signal is π-ωp
A bandpass, discrete-time signal has a spectrum occupying the frequency range 0< ωL ≤ |ω| ≤ ωH < π where ωH− ωL is the bandwidth
A precise definition of the bandwidth depends on applications: 80% of the energy
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2 The Unwrapped Phase Function
In numerical computation, when the computed phase function is outside the range [-π,π], the phase is computed modulo 2π, to bring the computed value to this range.
As the result, the phase functions of some sequences exhibit discontinuities of 2π radians in the plot.
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2 The Unwrapped Phase Function
Consider an alternate type of phase function that is a continuous function of ω derived from the original phase function by removing the discontinuities of 2π.
The process of removing the discontinuities is called “unwrapping the phase,” and the new phase function will be denoted as , with the subscript “c” indicating that it is a continuous function of ω.
( )c
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2 The Unwrapped Phase Function
The natural logarithm of the Fourier transform of the sequence x[n] can be expressed as
If exists, then its derivative with respect to ω also exists and is given by
( )jX e
ln ( ) ln ( ) ( )j jX e X e j
ln ( )jX e
( ) ( )1( )
j jre im
j
dX e dX ejX e d d
ln ( ) 1 ( )( )
j j
j
d X e dX ed X e d
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2 The Unwrapped Phase Function
The derivative of with respect to ω is also given by
The derivative of θ(ω) with respect to ω is given by the imaginary part of the right-hand side
ln ( )ln ( )jj d X e dd X e j
d d d
2
( ) ( )1 ( ) ( )( )
j jj jim re
re imj
d dX e dX eX e X ed d dX e
ln ( )jX e
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2 The Unwrapped Phase Function
The phase function θ(ω) can thus be defined unequivocally by its derivative :
with the constraint The phase function as defined is called the
unwrapped phase function. The unwrapped phase is a continuous function of ω.
d
dd
0
(0) 0
dd
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2 The Unwrapped Phase Function
If the above constraint is not satisfied, then the computed phase function will exhibit absolute jumps greater than π.
For unwrapping the phase, these jumps should be replaced with their 2π complements.
In Matlab, this can be done using the M-file unwrap.
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2 The Unwrapped Phase Function
Unwrapped phase spectrum of the Fourier transform
0 0.2 0.4 0.6 0.8 1-3
-2
-1
0
1
2
3
4Phase Spectrum
/
Pha
se, r
adia
ns
0 0.2 0.4 0.6 0.8 1-7
-6
-5
-4
-3
-2
-1
0Phase Spectrum
/P
hase
, rad
ians
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3 The Frequency Response of an LTI Discrete-time System
An LTI discrete-time system is completely characterized in the time-domain by its impulse response sequence {h[n]}
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3 The Frequency Response of an LTI Discrete-time System
Frequency response – A transform-domain representation of the LTI discrete-time system.
Such transform-domain representations provide additional insights into the behavior of such systems.
It is easier to design and implement these systems in the transformed-domain for certain applications.
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3 The Frequency Response of an LTI Discrete-time System
Most discrete-time signals encountered in practice can be represented as a linear combination of a very large, maybe infinite number of sinusoidal discrete-time signals of different angular frequencies.
Since a sinusoidal signal can be expressed in terms of an exponential signal, the response of the LTI system to an exponential input is of practical interest.
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3.1 Definition
An important property of an LTI system is that for certain types of input signals, called eigenfunctions, the output signal is the input signal multiplied by a complex constant.
Consider the following LTI system. We consider one such eigenfunction as the input.
h[n]x[n] y[n]
26
3.1 Definition
Its I-O relationship in the time domain is given by the convolution sum.
If the input is of the form
then
[ ] [ ] [ ] [ ] [ ]k k
y n x k h n k h k x n k
[ ] j nx n e n
( )[ ] [ ] [ ]j n k j k j n
k ky n h k e h k e e
( )jH e
27
3.1 Definition
Then we can write
It implies for a complex exponential input signal , the output of an LTI discrete-time system is also a complex exponential signal of the same frequency multiplied by a complex constant
Thus is an eigenfunction of the system
[ ] ( )j j ny n H e e
j ne
( )jH e
j ne
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3.1 Definition
The quantity is called the frequency response of the LTI discrete-time system that is a function of the input frequency ω and the system impulse response coefficients h[n].
provides the frequency-domain description of the system.
( )jH e
( )jH e
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3.1 Definition
In this course we shall be concerned with LTI discrete-time systems characterized by linear constant coefficient difference equations of the form:
0 0[ ] [ ]
N M
k kk k
d y n k p x n k
30
3.1 Definition
Applying the DTFT to the difference equation and making use of the linearity and the time-invariance properties, we arrive at the input-output relation in the transform-domain as
0 0( ) ( )
N Mj k j j k j
k kk k
d e Y e p e X e
y[n] x[n]DTFT
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3.1 Definition
Definition The DTFT of the impulse response of an LTI
system is called the Frequency Response of this system
2
arg{ ( )}
( ) ( ) ( ) ( )
( )j
jj j jre im
j j H e
H e H e H e jH e
H e e
magnitude response
phase response 32
3.1 Definition
In some cases, the magnitude function is specified in decibels as
where is called the gain function The negative of the gain function
is called the attenuation or loss function
10( ) 20 log ( ) dBjH e ( )
( ) ( )
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3.2 Frequency-Domain Characterization of the LTI Discrete-Time System
The convolution sum description of the LTI discrete-time system is given by
Taking the DTFT of both sides we obtain
[ ] [ ] [ ]k
y n h k x n k
( ) [ ] [ ]j j n
n k
Y e h k x n k e
34
3.2 Frequency-Domain Characterization of the LTI Discrete-Time System
Interchanging the summation signs on the right-hand side and rearranging we arrive at
( )
( ) [ ] [ ]
[ ] [ ]
[ ] [ ]
( ) ( )
j j n
k nl n k
j l k
k l
j l j k
k lj j
Y e h k x n k e
h k x l e
h k x l e e
H e X e
35
3.2 Frequency-Domain Characterization of the LTI Discrete-Time System
It follows from the previous equation
The output cannot contain sinusoidal components of frequencies that are not present in the input and the system.
As a result, if the output of a system has new frequency components, then the system is either nonlinear or time-varying or both.
( ) ( ) / ( )j j jH e Y e X e
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3.2 Frequency-Domain Characterization of the LTI Discrete-Time System
Example Convolution Sum Computation Using Fourier
Transformthe input sequence with |α|< 1the frequency response of the causal LTI system
with |β|< 1,
][][ nnx n
][][ nnh n
)1/(1)( jj eeX )1/(1)( jj eeH
)1)(1(1)()()(
jjjjj
eeeHeXeY
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3.2 Frequency-Domain Characterization of the LTI Discrete-Time System
)1)(1()()(
)1()1()(
jj
j
jjj
eeeBABA
eB
eAeY
1 1
0
[ ] [ ] [ ]
[ ] [ ]
n n
n n nk n k
k
y n n n
n n
A
B
38
3.3 Frequency Response of Discrete-Time Systems
Frequency Response of LTI FIR Discrete-Time Systems
Frequency Response of LTI IIR Discrete-Time Systems
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3.3-1 Frequency Response of LTI FIR Discrete-Time Systems
LTI FIR Discrete-Time System
The frequency response is
which is seen to be a polynomial in
2
1
1 2
N
k Ny n h k x n k N N
2
1
Nj j k
k NH e h k ew w
je
40
3.3-2 Frequency Response of LTI IIR Discrete-Time Systems
LTI IIR discrete-time systems are characterized by linear constant coefficient difference equations of the form
The frequency response is
M
0kk
N
0kk knxpknyd
N
0k
kjk
M
0k
kjk
j
jj
ed
ep
eXeY)e(H
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3.4 Frequency Response Computation using Matlab
The function freqz(h,w) can be used to determine the values of the frequency response vector h at a set of given frequency points w
From h, the real and imaginary parts can be computed using the functions real and imag, and the magnitude and phase functions using the functions abs and angle
42
3.4 Frequency Response Computation using Matlab
Example Consider a moving-average filter
Its frequency response is given by
1/ 0 1[ ]
0 otherwiseM n M
h n
,
,
1
0
1 2
1 1 11
sin 21sin 2
jMMj j n
jn
j M
eH e eM M e
Me
M
43
3.4 Frequency Response Computation using Matlab
The magnitude and phase responses of the moving-average filter are obtained
sin 21sin 2
j MH e
M
2
2
1 22
M
k
M kM
Program 4_3 can be used to generate the magnitude and gain responses of an M-point moving average filter as shown in the next slide 44
3.4 Frequency Response Computation using Matlab
0 0.2 0.4 0.6 0.8 10
0.2
0.4
0.6
0.8
1
Mag
nitu
de/
Magnitude Response
M=5M=14
0 0.2 0.4 0.6 0.8 1-200
-150
-100
-50
0
50
100
Phas
e, d
egre
es
/
Phase Response
M=5M=14
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3.5 The Concept of Filtering
One application of an LTI discrete-time system is to pass certain frequency components in an input sequence without any distortion (if possible) and to block other frequency components.
Such systems are called digital filters and one of the main subjects of discussion in this course.
46
3.5 The Concept of Filtering
The key to the filtering process is
It expresses an arbitrary input as a linear weighted sum of an infinite number of exponential sequences, or equivalently, as a linear weighted sum of sinusoidal sequences.
-
1[ ] ( )2
j j nx n X e e d
47
3.5 The Concept of Filtering
By appropriately choosing the values of the magnitude function of the LTI digital filter at frequencies corresponding to the frequencies of the sinusoidal components of the input, some of these components can be selectively heavily attenuated or filtered with respect to the others.
( )jH e
48
3.5 The Concept of Filtering
To understand the mechanism behind the design of frequency-selective filters, consider a real-coefficient LTI discrete-time system characterized by a magnitude function.
1, 0( )
0,cj
c
H e
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3.5 The Concept of Filtering
We apply an input
to this system
Because of linearity, the output of this system is of the form
1 2 1 2[ ] cos cos , 0 cx n A n B n
1
2
1 1
2 2
[ ] ( ) cos( ( ))
( ) cos( ( ))
j
j
y n A H e n
B H e n
Eigen-function, conjugate-symmetric for real h[n] 50
3.5 The Concept of Filtering
As
the output reduces to
Thus, the system acts like a lowpass filter In the following example, we consider the
design of a very simple digital filter.
1( ) 1jH e 2( ) 0jH e
11 1[ ] ( ) cos( ( ))jy n A H e n
51
3.5 The Concept of Filtering
Example Design of a high pass digital filter
The input which consists of two frequency components 0.1 rad/sample and 0.4 rad/sample.
For simplicity, assume the filter to be an FIR filter of length-3 with an impulse response:
[ ] cos(0.1 ) cos(0.4 ) [ ]x n n n u n
52
3.5 The Concept of Filtering
Note that h[n] is a linear phase FIR filterwhich will be discussed in the latter chapters
The frequency response of this filter is given by
0 1 2 n
h(n)
2( ) [0] [1] [2](2 cos )
j j j
j
H e h h e h ee
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3.5 The Concept of Filtering
The magnitude and phase functions are
In order to block the low-frequency component, the magnitude function at ω = 0.1 should be equal to zero
Likewise, to pass the high-frequency component, the magnitude function at ω = 0.4should be equal to one
( ) 2 cosjH e ( )
54
3.5 The Concept of Filtering
Thus, the two conditions that must be satisfied are
Solving the above two equations we get
Thus the output-input relation of the FIR filter is given by
2 cos 0.1 0 2 cos 0.4 1
6.76195 13.456335
[ ] 6.76195 [ ] 13.456335 [ 1]6.76195 [ 2]
y n x n x nx n
550 20 40 60 80 100-1
0
1
2
3
4
Am
plitu
de
Time index n
y(n)x2(n)
x1(n)
3.5 The Concept of Filtering
Figure below shows the plots generated by running program 4_4
56
3.5 The Concept of Filtering
Figure below shows the frequency response of this highpass filter
0 0.1 0.2 0.3 0.40
0.2
0.4
0.6
0.8
1
rad/sampleH
(ej
)
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4 Definition of Phase and Group delays
They are two important additional parameters that characterize the form of the output response y[n] of an LTI discrete-time system excited by an input signal x[n] composed of a weighted linear combination of sinusoidal sequences.
58
4.1 Definition of Phase Delay
The output h[n] of a frequency-selective LTI discrete-time system with a frequency response exhibits some delay relativeto the input caused by the nonzero phase response of the system
For an input
( )jH e
( ) arg ( )jH e
0[ ] cos( )x n A n n
59
4.1 Definition of Phase Delay
The output is
Thus, the output lags in phase by radians
Rewriting the above equation we get
00 0[ ] ( ) cos( ( ) )jy n A H e n
0( )
00
0
( )[ ] ( ) cosjy n A H e n
Proof
60
4.1 Definition of Phase delays
Phase delay
The phase delay of s discrete-time signal leads to a phase shift in the output of the system with respect to the input, with the amount of shift depending on the frequency ω
The output y[n] will not be a delayed replica of the input x[n] unless the phase delay is an integer.
00
0
( )( )p
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4.1 Definition of Phase delays
Now consider the case when the input signal contains many sinusoidal components with different frequencies that are not harmonically related
In this case, each component of the input will go through different phase delays when processed by a frequency-selective LTI discrete-time system
Then, the output signal, in general, will not look like the input signal. 62
4.2 Definition of Group delays
To develop the necessary expression, consider a discrete-time signal x [n] obtained by a double-sideband suppressed carrier (DSB-SC)modulation with a carrier frequency of a low-frequency sinusoidal signal of frequency
c0
0
0 0
[ ] cos( ) cos( )
cos( ) cos( )2 2
c
l u
l c u c
x n A n nA An n
63
4.2 Definition of Group delays
Let the input be processed by an LTI discrete-time system with a frequency response satisfying the condition
The output y[n] is then given by
( )jH e
( ) 1 forjl uH e
[ ] cos ( ) cos ( )2 2l l u uA Ay n n n
0( ) ( ) ( ) ( )
cos cos2 2
u l u lcA n n
64
4.2 Definition of Group delays
Note: The output is also in the form of a modulated carrier signal with the same carrier frequency and the same modulation frequency as the input.
However, the two components have different phase lags relative to their corresponding components in the input
c0
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4.2 Definition of Group delays
Now consider the case when the modulated input is a narrow band signal with the frequencies and very close to the carrier frequency , i.e. is very small
In the neighborhood of we can express the phase response as
by making a Taylor’s series expansion and keeping only the first two terms
u0
lc
c( )
( )( ) ( ) ( )c
c cd
d
66
4.2 Definition of Group delays
Using the above formula, we now evaluate the time delays of the carrier and the modulating components:
In the case of the carrier signal we have
which is seen to be the same as the phase delay if only the carrier signal is passed through the system
( ) ( ) ( )2
u l c
c c
67
4.2 Definition of Group delays
In the case of the modulating component we have
The parameter
is called the group delay or envelope delaycaused by the system at
0
( ) ( ) ( ) ( ) ( )2
c
u l u l
u l
dd
( )( )
c
g cd
d
c 68
4.2 Definition of Group delays
The group delay is a measure of the linearity of the phase function as a function of the frequency
It is the time delay between the waveforms of underlying continuous-time signals whose sampled versions, sampled at t = nT, are precisely the input and the output discrete-time signals
If the phase function and the angular frequency ωare in radians per second, then the group delay is in seconds
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4.3 Phase and Group delays
Figure below illustrates the evaluation of the phase delay and the group delay
70
4.3 Definition of Phase and Group delays
As can be seen, the group delay is the negative of the slope of the phase function at a frequency ,
Whereas the phase delay is the negative of the slope of the straight line from the origin to the point on the phase function plot.
0 g
0 p
0
[ )]0 0ω , θ(ω
71
4.3 Phase and Group delays
Figure below shows the waveform of an amplitude-modulated input and the output generated by an LTI system
72
4.3 Phase and Group delays
Example The phase function of the FIR Filter
is Hence its group delay is given by
[ ] [ ] [ 1] [ 2]y n x n x n x n ( )
( ) 1g
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19
73
4.3 Phase and Group delays
Example Consider an LTI continuous-time system with
a frequency response and excited by a narrow-band amplitude modulated continuous-time signal given by
where a(t) is a lowpass modulating signal with a band-limited continuous-time Fourier transform given by
aja aH j H j e q
cosa cx t a t t
00, A j 74
4.3 Phase and Group delays
We assume that in the frequency range
the frequency response of the continuous-time system has a constant magnitude and a linear phase; that is,
0 0| |c c
a a cH j H j
c
aa a c c
c p c c g c
ddq
q q
t t
75
4.3 Phase and Group delays
The continuous-time Fourier transform of the input signal is of the form
of the LTI continuous-time system is given by
12a c cX j A j A j
)(txa
tya
cosa g c c p cy t a t t
76
4.3 Phase and Group delays
0 2 4 6 8 10-1
0
1
Time t
Am
plitu
de0 2 4 6 8 10
-1
0
1
Time tA
mpl
itude
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20
77
4.3 Phase and Group delays
The group delay is precisely the delay of the envelope of the input signal , whereas the phase delay is the delay of the carrier signal.
The carrier component at the output is delayed by the phase delay and the envelope of the output is delayed by the group delay relative to the waveform of the continuous-time input signal in the previous slide
cg
cp txa( )a t
78
4.3 Phase and Group delays
The waveform of the underlying continuous time output shows distortion when the group delay of the LTI system is not constant over the bandwidth of the modulated signal
In the case of LTI systems with a wide-band frequency response, the two delays do not have any physical meanings.
79
4.3 Phase and Group delays
If the distortion is unacceptable, a delay equalizer is usually cascaded with the LTI system so that the overall group delay of the cascade is approximately linear over the band of interest.
To keep the magnitude response of the parent LTI system unchanged, the equalizer must have a constant magnitude response at all frequencies
80
4.4 Phase and Group delay Computation Using Matlab
Phase delay and group delay can be computed using the function phasedelay, grpdelayrespectively
Figures in the next slide shows the phase delay and group delay of the DTFT
2
2
0.1367(1 )( )1 0.5335 0.7265
jj
j j
eH ee e
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81
4.4 Phase and Group delay Computation Using Matlab
0 0.2 0.4 0.6 0.8 1-150
-100
-50
0
/
Phas
e de
lay,
sam
ples
0 0.2 0.4 0.6 0.8 10
1
2
3
4
5
6
7
/G
roup
del
ay, s
ampl
es
2726542528.053353098.01)1(136728736.0
jj
jj
eeeeH