1 chapter 4. microwave network analysis it is much easier to apply the simple and intuitive idea of...

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1 Chapter 4. Microwave Network Analysis It is much easier to apply the simple and intuitive idea of circuit analysis to a microwave problem than it is to solve Maxwell’s equations for the same problem. Maxwell’s equations for a given problem is complete, it gives the E & H fields at all points in space. Usually we are interested in only the V & I at a set of terminals, the power flow through a device, or some other type of “global” quantity. A field analysis using Maxwell’s equations for problems would be hopelessly difficult.

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Page 1: 1 Chapter 4. Microwave Network Analysis It is much easier to apply the simple and intuitive idea of circuit analysis to a microwave problem than it is

1

Chapter 4. Microwave Network Analysis

• It is much easier to apply the simple and intuitive idea of circuit analysis to a microwave problem than it is to solve Maxwell’s equations for the same problem.

• Maxwell’s equations for a given problem is complete, it gives the E & H fields at all points in space.

• Usually we are interested in only the V & I at a set of terminals, the power flow through a device, or some other type of “global” quantity.

• A field analysis using Maxwell’s equations for problems would be hopelessly difficult.

Page 2: 1 Chapter 4. Microwave Network Analysis It is much easier to apply the simple and intuitive idea of circuit analysis to a microwave problem than it is

2

4.1 Impedance and Equivalent Voltages and CurrentsEquivalent Voltages and Currents• The voltage of the + conductor relative to the –

conductor

• After having defined and determined a voltage, current, and characteristic impedance, we can proceed to apply the circuit theory for transmission lines to characterize this line as a circuit element.

0

C

V E dl

I H dl

VZ

I

Page 3: 1 Chapter 4. Microwave Network Analysis It is much easier to apply the simple and intuitive idea of circuit analysis to a microwave problem than it is

3

Figure 4.1 (p. 163)Electric and magnetic field lines for an arbitrary two-conductor TEM line.

Page 4: 1 Chapter 4. Microwave Network Analysis It is much easier to apply the simple and intuitive idea of circuit analysis to a microwave problem than it is

4

Figure 4.2 (p. 163)Electric field lines for the TE10 mode of a rectangular waveguide.

10

( , , ) sin ( , )

( , , ) sin ( , )

j z j zy y

j z j zx x

TE

j a xE x y z A e Ae x y e

aj a x

H x y z A e Ah x y ea

Page 5: 1 Chapter 4. Microwave Network Analysis It is much easier to apply the simple and intuitive idea of circuit analysis to a microwave problem than it is

5

• There is no “correct” voltage in the sense of being unique.

• There are many ways to define equivalent voltage, current, and impedance for waveguides.– V&I are defined only for a particular waveguide mode.

– The equivalent V&I should be defined so that their product gives the power flow of the mode.

– V/I for a single traveling wave should be equal to Z0 of the line. This impedance may be chosen arbitrarily, but is usually selected as equal to the wave impedance of the line.

sin j z

y

j a xV A e dy

a

( / 2,0 ) ( 0,0 )V x a y b V x y b

Page 6: 1 Chapter 4. Microwave Network Analysis It is much easier to apply the simple and intuitive idea of circuit analysis to a microwave problem than it is

6

• For an arbitrarily waveguide mode, the transverse fields

where e and h are the transverse field variations of the mode. Since Et & Ht are related by Zw,

• Defining equivalent voltage and current waves as

1

2

( , )( , , ) ( , )( ) ( )

( , )( , , ) ( , )( ) ( )

j z j z j z j zt

j z j z j z j zt

e x yE x y z e x y A e A e V e V e

C

h x yH x y z h x y A e A e I e V e

C

ˆ ( , )( , )

w

z e x yh x y

Z

0

( ) ,

( ) with

j z j z

j z j z

V z V e V e

V VI z I e I e Z

I I

Page 7: 1 Chapter 4. Microwave Network Analysis It is much easier to apply the simple and intuitive idea of circuit analysis to a microwave problem than it is

7

• The complex power flow for the incident wave

• Since we want this power to be (1/2)V+I+*,

where the surface integration is over the cross section of the waveguide.

• If it is desired to have Z0 = Zw,

2

1 2

1ˆ ˆ| |

2 2S S

V IP A e h zds e h zds

C C

1 2 ˆS

C C e h zds

10

2

V V CZ

I I C

1

2

( or )w TE TM

CZ Z Z

C

Page 8: 1 Chapter 4. Microwave Network Analysis It is much easier to apply the simple and intuitive idea of circuit analysis to a microwave problem than it is

8

• For higher order modes,

• Ex 4.1

1 1 1

1 2 2

( , , ) ( ) ( , )

( , , ) ( ) ( , )

n n

n n

Nj z j zn n

t nn n n

Nj z j zn n

t nn n n

V VE x y z e e e x y

C C

I IH x y z e e h x y

C C

Page 9: 1 Chapter 4. Microwave Network Analysis It is much easier to apply the simple and intuitive idea of circuit analysis to a microwave problem than it is

9

The Concept of Impedance

• Various types of impedance– Intrinsic impedance ( ) of the medium: depends

on the material parameters of the medium, and is equal to the wave impedance for plane waves.

– Wave impedance ( ): a characteristic of the particular type of wave. TEM, TM and TE waves each have different wave impedances which may depend on the type of the line or guide, the material, and the operating frequency.

– Characteristic impedance ( ): the ratio of V/I for a traveling wave on a transmission line. Z0 for TEM wave is unique. TE and TM waves are not unique.

/

/ 1/w t t wZ E H Y

0 01/ /Z Y L C

Page 10: 1 Chapter 4. Microwave Network Analysis It is much easier to apply the simple and intuitive idea of circuit analysis to a microwave problem than it is

10

Ex 4.2

Figure 4.3 (p. 167)Geometry of a partially filled waveguide and its transmission line equivalent for Example 4.2.

Page 11: 1 Chapter 4. Microwave Network Analysis It is much easier to apply the simple and intuitive idea of circuit analysis to a microwave problem than it is

11

Figure 4.4 (p. 168)An arbitrary one-port network.

Page 12: 1 Chapter 4. Microwave Network Analysis It is much easier to apply the simple and intuitive idea of circuit analysis to a microwave problem than it is

12

• The complex power delivered to this network is:

where Pl is real and represents the average power dissipated by the network.

• If we define real transverse modal fields, e and h, over the terminal plane of the network such that

with a normalization

12 ( )

2 l m eSP E H ds P j W W

( , , ) ( ) ( , )

( , , ) ( ) ( , )

j zt

j zt

E x y z V z e x y e

H x y z I z h x y e

1Se h ds

1 1

2 2SP VI e h ds VI

Page 13: 1 Chapter 4. Microwave Network Analysis It is much easier to apply the simple and intuitive idea of circuit analysis to a microwave problem than it is

13

• The input impedance is

• If the network is lossless, then Pl = 0 and R = 0. Then Zin is purely imaginary, with a reactance

2 2 21 12 2

2 ( )l m ein

P j W WV VI PZ R jX

I I I I

2

4 ( )m eW WX

I

Page 14: 1 Chapter 4. Microwave Network Analysis It is much easier to apply the simple and intuitive idea of circuit analysis to a microwave problem than it is

14

Even and Odd Properties of Z(ω) and Γ(ω)

• Consider the driving point impedance, Z(ω), at the input port of an electrical network. V(ω) = I(ω) Z(ω).

• Since v(t) must be real v(t) = v*(t),

Re{V(ω)} is even in ω, Im{V(ω)} is odd in ω. I(ω) holds the same as V(ω).

1( ) ( )

2j tv t V e d

( ) ( ) ( )

( ) ( )

j t j t j tV e d V e d V e d

V V

( ) ( ) ( ) ( ) ( ) ( ) ( ) ( )V Z I Z I V Z I

Page 15: 1 Chapter 4. Microwave Network Analysis It is much easier to apply the simple and intuitive idea of circuit analysis to a microwave problem than it is

15

• The reflection coefficient at the input port

0 0

0 0

0 0

0 0

2 2

( ) ( ) ( )( )

( ) ( ) ( )

( ) ( ) ( ) ( )( ) ( )

( ) ( ) ( ) ( )

( ) ( ) ( ) ( ) ( ) ( )

Z Z R Z jX

Z Z Z Z jX

R Z jX R Z jX

Z Z jX Z Z jX

Page 16: 1 Chapter 4. Microwave Network Analysis It is much easier to apply the simple and intuitive idea of circuit analysis to a microwave problem than it is

16

4.2 Impedance and Admittance Matrices

• At the nth terminal plane, the total voltage and current is as seen from (4.8) when z = 0.

• The impedance matrix

• Similarly,

where

, n n n n n nV V V I I I

V Z I

I Y V

11 12 1

121

1

N

N NN

Y Y Y

YY Z

Y Y

Page 17: 1 Chapter 4. Microwave Network Analysis It is much easier to apply the simple and intuitive idea of circuit analysis to a microwave problem than it is

17

Figure 4.5 (p. 169)An arbitrary N-port microwave network.

Page 18: 1 Chapter 4. Microwave Network Analysis It is much easier to apply the simple and intuitive idea of circuit analysis to a microwave problem than it is

18

• Zij can be defined as

In words, Zij can be found by driving port j with the current Ij, open-circuiting all other ports (so Ik=0 for k≠j), and measuring the open-circuit voltage at port i.

• Zii: input impedance seen looking into port i when all other ports are open.

• Zij: transfer impedance between ports i and j when all other ports are open.

• Similarly,

0 for k

iij

j I k j

VZ

I

0 for k

iij

j V k j

IY

V

Page 19: 1 Chapter 4. Microwave Network Analysis It is much easier to apply the simple and intuitive idea of circuit analysis to a microwave problem than it is

19

Reciprocal Networks

• Let Fig. 4.5 to be reciprocal (no active device, ferrites, or plasmas), with short circuits placed at all terminal planes except those of ports 1 and 2.

• Let Ea, Ha and Eb, Hb be the fields anywhere in the network due to 2 independent sources, a and b, located somewhere in the network.

• From the reciprocity theorem,

a b b aS SE H ds E H ds

Page 20: 1 Chapter 4. Microwave Network Analysis It is much easier to apply the simple and intuitive idea of circuit analysis to a microwave problem than it is

20

• The fields due to sources a and b at the terminal planes t1 and t2: (4.31)

where e1, h1 and e2, h2 are the transverse modal fields of port 1 and 2. Therefore,

where S1, S2 are the cross-sectional areas at the terminal planes of ports 1 and 2.

• Comparing (4.31) to (4.6), C1 = C2 = 1 for each port, so that from (4.10).

1 1 1 1 1 1

1 1 1 1 1 1

2 2 2 2 2 2

2 2 2 2 2 2

,

,

,

,

a a a a

b b b b

a a a a

b b b b

E V e H I h

E V e H I h

E V e H I h

E V e H I h

1 2

1 1 1 1 1 1 2 2 2 2 2 2 0a b b a a b b aS SV I V I e h ds V I V I e h ds

1 21 1 2 2S S

e h ds e h ds

Page 21: 1 Chapter 4. Microwave Network Analysis It is much easier to apply the simple and intuitive idea of circuit analysis to a microwave problem than it is

21

• This leads to• For 2 port,

Generally,

1 1 1 1 2 2 2 2 0a b b a a b b aV I V I V I V I

1 11 1 12 2 2 21 1 22 2, I Y V Y V I Y V Y V

1 11 1 12 2 1 11 1 12 2

2 21 1 22 2 2 21 1 22 2 0

a b b b a a

a b b b a a

V Y V Y V V Y V Y V

V Y V Y V V Y V Y V

1 2 1 2 12 21 0a b b aV V V V Y Y

12 21Y Y

ij jiY Y

Page 22: 1 Chapter 4. Microwave Network Analysis It is much easier to apply the simple and intuitive idea of circuit analysis to a microwave problem than it is

22

Lossless Networks

• Consider a reciprocal lossless N-port network.

• If the network is lossless, Re{Pav} = 0.

• Since the Ins are independent, only nth current is taken.

1 11 1 1 12 2 2 21 1

1 1

1 1 1[ ] [ ] [ ][ ] [ ] [ ] [ ][ ]

2 2 21

( )21

2

tt tav

N N

m mn nn m

P V I Z I I I Z I

I Z I I Z I I Z I

I Z I

2Re Re 0n nn n n nnI Z I I Z Re 0nnZ

Page 23: 1 Chapter 4. Microwave Network Analysis It is much easier to apply the simple and intuitive idea of circuit analysis to a microwave problem than it is

23

• Take Im and In only

• Since (InIm*+ ImIn

*) is purely real, Re{Zmn} = 0,.

• Therefore, Re{Zmn} = 0 for any m, n.

Ex 4.3

Re 0n m m n mnI I I I Z

Page 24: 1 Chapter 4. Microwave Network Analysis It is much easier to apply the simple and intuitive idea of circuit analysis to a microwave problem than it is

24

4.3 The Scattering Matrix

• The scattering matrix relates the voltage waves incident on the ports to those reflected from the ports.

• The scattering parameters can be calculated using network analysis technique. Otherwise, they can be measured directly with a vector network analyzer.

• Once the scattering matrix is known, conversion to other matrices can be performed.

• Consider the N-port network in Fig. 4.5.

Page 25: 1 Chapter 4. Microwave Network Analysis It is much easier to apply the simple and intuitive idea of circuit analysis to a microwave problem than it is

25

11 12 11 1

212 2

1

N

N NNN N

S S SV V

SV V

S SV V

or

• Sii the reflection coefficient seen looking into port i when all other ports are terminated in matched loads,

• Sij the transmission coefficient from port j to port i when all other ports are terminated in matched loads.

V S V

0 for k

iij

j V k j

VS

V

Page 26: 1 Chapter 4. Microwave Network Analysis It is much easier to apply the simple and intuitive idea of circuit analysis to a microwave problem than it is

26

Figure 4.7 (p. 175)A photograph of the Hewlett-Packard HP8510B Network Analyzer. This test instrument is used to measure the scattering parameters (magnitude and phase) of a one- or two-port microwave network from 0.05 GHz to 26.5 GHz. Built-in microprocessors provide error correction, a high degree of accuracy, and a wide choice of display formats. This analyzer can also perform a fast Fourier transform of the frequency domain data to provide a time domain response of the network under test. Courtesy of Agilent Technologies.

Page 27: 1 Chapter 4. Microwave Network Analysis It is much easier to apply the simple and intuitive idea of circuit analysis to a microwave problem than it is

27

Figure 4.8 (p. 176)A matched 3B attenuator with a 50 Ω Characteristic impedance

Ex.4, Evaluation of Scattering Parameters

Page 28: 1 Chapter 4. Microwave Network Analysis It is much easier to apply the simple and intuitive idea of circuit analysis to a microwave problem than it is

28

• Show how [S] [Z] or [Y]. Assume Z0n are all identical, for convenience Z0n = 1.

where

Therefore,• For a one-port network,

,n n n n n n n nV V V I I I V V

[ ][ ] [ ][ ] [ ][ ] [ ] [ ] [ ]

([ ] [ ])[ ] ([ ] [ ])[ ]

Z I Z V Z V V V V

Z U V Z U V

1 0 0

0 1[ ]

0 1

U

1 1[ ] [ ][ ] ([ ] [ ]) ([ ] [ ])S V V Z U Z U

1111

11

1

1

zS

z

Page 29: 1 Chapter 4. Microwave Network Analysis It is much easier to apply the simple and intuitive idea of circuit analysis to a microwave problem than it is

29

• To find [Z],

Reciprocal Networks and Lossless Networks• As in Sec. 4.2, the [Z] and [Y] are symmetric for

reciprocal networks, and purely imaginary for lossless networks.

• From

1

[ ][ ] [ ][ ] [ ] [ ]

[ ] ([ ] [ ])([ ] [ ])

Z S U S Z U

Z U S U S

1

21

[ ] ([ ] [ ])[ ]2

n n nV V I

V Z U I

1

21

[ ] ([ ] [ ])[ ]2

n n nV V I

V Z U I

1

1

1

[ ] ([ ] [ ])([ ] [ ]) [ ]

[ ] ([ ] [ ])([ ] [ ])

[ ] ([ ] [ ]) ([ ] [ ])tt t

V Z U Z U V

S Z U Z U

S Z U Z U

Page 30: 1 Chapter 4. Microwave Network Analysis It is much easier to apply the simple and intuitive idea of circuit analysis to a microwave problem than it is

30

• If the network is reciprocal, [Z]t = [Z].

• If the network is lossless, no real power delivers to the network.

1[ ] ([ ] [ ]) ([ ] [ ])

[ ] [ ]

t

t

S Z U Z U

S S

1 1Re{[ ] [ ] } Re{([ ] [ ] )([ ] [ ] )}

2 21

Re{([ ] [ ] [ ] [ ] [ ] [ ] [ ] [ ] )}21 1

[ ] [ ] [ ] [ ] 02 2

t t tav

t t t t

t t

P V I V V V V

V V V V V V V V

V V V V

[ ] [ ] [ ] [ ]

([ ][ ]) ([ ][ ])

[ ] [ ] [ ] [ ]

t t

t

t t

V V V V

S V S V

V S S V

Page 31: 1 Chapter 4. Microwave Network Analysis It is much easier to apply the simple and intuitive idea of circuit analysis to a microwave problem than it is

31

• For nonzero [V+], [S]t[S]*=[U], or [S]*={[S]t}-1. Unitary matrix

• If i = j,

• If i ≠ j,

• Ex 4.5 Application of Scattering Parameters• The S parameters of a network are properties only of

the network itself (assuming the network in linear), and are defined under the condition that all ports are matched.

1

, for all ,

where 1 if , 0 if .

N

ki kj ijk

ij ij

S S i j

i j i j

1

1N

ki kik

S S

1

0.N

ki kjk

S S

Page 32: 1 Chapter 4. Microwave Network Analysis It is much easier to apply the simple and intuitive idea of circuit analysis to a microwave problem than it is

32

A Shift in Reference Planes

Figure 4.9 (p. 181)Shifting reference planes for an N-port network.

Page 33: 1 Chapter 4. Microwave Network Analysis It is much easier to apply the simple and intuitive idea of circuit analysis to a microwave problem than it is

33

• [S]: the scattering matrix at zn = 0 plane.

• [S']: the scattering matrix at zn = ln plane.[ ] [ ][ ],

[ ] [ ][ ]

V S V

V S V

,n nj jn n n nV V e V V e

1 1

1 1

0 0

0 0

0 0

0 0

N N

N N

j j

j j

j j

j j

e e

V S V

e e

e e

V S V

e e

Page 34: 1 Chapter 4. Microwave Network Analysis It is much easier to apply the simple and intuitive idea of circuit analysis to a microwave problem than it is

34

1 10 0

0 0N N

j j

j j

e e

S S

e e

Page 35: 1 Chapter 4. Microwave Network Analysis It is much easier to apply the simple and intuitive idea of circuit analysis to a microwave problem than it is

35

Generalized Scattering Parameters

Figure 4.10 (p. 181)An N-port network with different characteristic impedances.

Page 36: 1 Chapter 4. Microwave Network Analysis It is much easier to apply the simple and intuitive idea of circuit analysis to a microwave problem than it is

36

0 0/ , /n n n n n na V Z b V Z

0

00

( )

1( )

n n n n n n

n n n n n nn

V V V Z a b

I V V Z a bZ

2 2

2 2

1 1Re Re

2 21 1

2 2

n n n n n n n n n

n n

P V I a b b a b a

a b

Page 37: 1 Chapter 4. Microwave Network Analysis It is much easier to apply the simple and intuitive idea of circuit analysis to a microwave problem than it is

37

• The generalized scattering matrix can be used to relate the incident and reflected waves,

b S a

0 for k

iij

j a k j

bS

a

_

0 for k

iij

j V k j

VS

V

Page 38: 1 Chapter 4. Microwave Network Analysis It is much easier to apply the simple and intuitive idea of circuit analysis to a microwave problem than it is

38

Figure on page 183

Page 39: 1 Chapter 4. Microwave Network Analysis It is much easier to apply the simple and intuitive idea of circuit analysis to a microwave problem than it is

39

4.4 The Transmission (ABCD) Matrix

• The ABCD matrix of the cascade connection of 2 or more 2-port networks can be easily found by multiplying the ABCD matrices of the individual 2-ports.

Page 40: 1 Chapter 4. Microwave Network Analysis It is much easier to apply the simple and intuitive idea of circuit analysis to a microwave problem than it is

40

1 2 2

1 2 2

V AV BI

I CV DI

1 2

1 2

V VA B

I C D I

1 21 1

1 11 2

V VA B

C DI I

32 2 2

2 22 3

VV A B

C DI I

31 1 1 2 2

1 1 2 21 3

VV A B A B

C D C DI I

Ex. 4.6 Evaluation of ABCD Parameters

Page 41: 1 Chapter 4. Microwave Network Analysis It is much easier to apply the simple and intuitive idea of circuit analysis to a microwave problem than it is

41

Relation to Impedance Matrix

• From the Z parameters with -I2 ,

1 1 11 2 12

1 1 21 2 22

V I Z I Z

I I Z I Z

2

2 2 2

2

2

1 1 1111 21

2 1 210

1 1 11 2 12 1 1 22 11 22 12 2111 12 11 12

2 2 2 1 21 210 0 0

1 121

2 1 210

1 2 2222 21

2 20

/

1/

/

I

V V V

I

V

V I ZA Z Z

V I Z

V I Z I Z I I Z Z Z Z ZB Z Z Z Z

I I I I Z Z

I IC Z

V I Z

I I ZD Z Z

I I

Page 42: 1 Chapter 4. Microwave Network Analysis It is much easier to apply the simple and intuitive idea of circuit analysis to a microwave problem than it is

42

• If the network is reciprocal, Z12=Z21, and AD-BC=1.

Equivalent Circuits for 2-port Networks• Table 4-2• A transition between a coaxial line and a microstrip

line. Because of the physical discontinuity in the transition from a coaxial line to a microstrip line, electric and/or magnetic energy can be stored in the vicinity of the junction, leading to reactive effects.

Page 43: 1 Chapter 4. Microwave Network Analysis It is much easier to apply the simple and intuitive idea of circuit analysis to a microwave problem than it is

43

Figure 4.12 (p. 188)A coax-to-microstrip transition and equivalent circuit representations. (a) Geometry of the transition. (b) Representation of the transition by a “black box.” (c) A possible equivalent circuit for the transition [6].

Page 44: 1 Chapter 4. Microwave Network Analysis It is much easier to apply the simple and intuitive idea of circuit analysis to a microwave problem than it is

44

Figure 4.13 (p. 188)Equivalent circuits for a reciprocal two-port network. (a) T equivalent. (b) π equivalent.

Page 45: 1 Chapter 4. Microwave Network Analysis It is much easier to apply the simple and intuitive idea of circuit analysis to a microwave problem than it is

45

4.5 Signal Flow Graphs

• Very useful for the features and the construction of the flow transmitted and reflected waves.

• Nodes: Each port, i, of a microwave network has 2 nodes, ai and bi. Node ai is identified with a wave entering port i, while node bi is identified with a wave reflected from port i. The voltage at a node is equal to the sum of all signals entering that node.

• Branches: A branch is directed path between 2 nodes, representing signal flow from one node to another. Every branch has an associated S parameter or reflection coefficient.

Page 46: 1 Chapter 4. Microwave Network Analysis It is much easier to apply the simple and intuitive idea of circuit analysis to a microwave problem than it is

46

Figure 4.14 (p. 189)The signal flow graph representation of a two-port network. (a) Definition of incident and reflected waves. (b) Signal flow graph.

Page 47: 1 Chapter 4. Microwave Network Analysis It is much easier to apply the simple and intuitive idea of circuit analysis to a microwave problem than it is

47

Figure 4.15 (p. 190)The signal flow graph representations of a one-port network and a source. (a) A one-port network and its flow graph. (b) A source and its flow graph.

Page 48: 1 Chapter 4. Microwave Network Analysis It is much easier to apply the simple and intuitive idea of circuit analysis to a microwave problem than it is

48

Decomposition of Signal Flow Graphs

• A signal flow graph can be reduced to a single branch between 2 nodes using the 4 basic decomposition rules below, to obtain any desired wave amplitude ratio.– Rule 1 (Series Rule): V3 = S32V2 = S32S21V1 .

– Rule 2 (Parallel Rule): V2 = SaV1 + SbV1 = (Sa + Sb)V1.

– Rule 3 (Self-Loop Rule): V2 = S21V1 + S22V2, V3 = S32V2.

V3 = S32S21V1/(1-S22)

– Rule 4 (Splitting Rule): V4 = S42V2 = S21S42V1.

Page 49: 1 Chapter 4. Microwave Network Analysis It is much easier to apply the simple and intuitive idea of circuit analysis to a microwave problem than it is

49

Figure 4.16 (p. 191)Decomposition rules. (a) Series rule.

(b) Parallel rule. (c) Self-loop rule. (d) Splitting rule.

Page 50: 1 Chapter 4. Microwave Network Analysis It is much easier to apply the simple and intuitive idea of circuit analysis to a microwave problem than it is

50

Ex 4.7 Application of Signal Flow Graph

Figure 4.17 (p. 192)A terminated two-port network.

Page 51: 1 Chapter 4. Microwave Network Analysis It is much easier to apply the simple and intuitive idea of circuit analysis to a microwave problem than it is

51

Figure 4.18 (p. 192)Signal flow path for the two-port network with general source and load impedances of Figure 4.17.

Page 52: 1 Chapter 4. Microwave Network Analysis It is much easier to apply the simple and intuitive idea of circuit analysis to a microwave problem than it is

52

Figure 4.19 (p. 192)Decompositions of the flow graph of Figure 4.18 to find Γin = b1/a1 and Γout = b2/a2. (a) Using Rule 4 on node a2. (b) Using Rule 3 for the self-loop at node b2. (c) Using Rule 4 on node b1. (d) Using Rule 3 for the self-loop at node a1.

Page 53: 1 Chapter 4. Microwave Network Analysis It is much easier to apply the simple and intuitive idea of circuit analysis to a microwave problem than it is

53

Figure 4.20 (p. 193)Block diagram of a network analyzer measurement of a two-port device.

Page 54: 1 Chapter 4. Microwave Network Analysis It is much easier to apply the simple and intuitive idea of circuit analysis to a microwave problem than it is

54

Figure 4.21a (p. 194)Block diagram and signal flow graph for the Thru connection.

Page 55: 1 Chapter 4. Microwave Network Analysis It is much easier to apply the simple and intuitive idea of circuit analysis to a microwave problem than it is

55

Figure 4.21b (p. 194)Block diagram and signal flow graph for the Reflect connection.

Page 56: 1 Chapter 4. Microwave Network Analysis It is much easier to apply the simple and intuitive idea of circuit analysis to a microwave problem than it is

56

Figure 4.21c (p. 194)Block diagram and signal flow graph for the Line connection.

Page 57: 1 Chapter 4. Microwave Network Analysis It is much easier to apply the simple and intuitive idea of circuit analysis to a microwave problem than it is

57

Figure 4.22 (p. 198)Rectangular waveguide discontinuities.

Page 58: 1 Chapter 4. Microwave Network Analysis It is much easier to apply the simple and intuitive idea of circuit analysis to a microwave problem than it is

58

Figure 4.23 (p. 199)Some common microstrip discontinuities. (a) Open-ended microstrip. (b) Gap in microstrip. (c) Change in width. (d) T-junction. (e) Coax-to-microstrip junction.

Page 59: 1 Chapter 4. Microwave Network Analysis It is much easier to apply the simple and intuitive idea of circuit analysis to a microwave problem than it is

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Figure 4.24 (p. 200)Geometry of an H-plane step (change in width) in rectangular waveguide.

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Figure 4.25 (p. 203)Equivalent inductance of an H-plane asymmetric step.

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Figure on page 204Reference: T.C. Edwards, Foundations for Microwave Circuit Design, Wiley, 1981.

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Figure 4.26 (p. 205)An infinitely long rectangular waveguide with surface current densities at z = 0.

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Figure 4.27 (p. 206)An arbitrary electric or magnetic current source in an infinitely long waveguide.

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Figure 4.28 (p. 208)A uniform current probe in a rectangular waveguide.

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Figure 4.29 (p. 210)Various waveguide and other transmission line configurations using aperture coupling. (a) Coupling between two waveguides wit an aperture in the common broad wall. (b) Coupling to a waveguide cavity via an aperture in a transverse wall. (c) Coupling between two microstrip lines via an aperture in the common ground plane. (d) Coupling from a waveguide to a stripline via an aperture.

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Figure 4.30 (p. 210)Illustrating the development of equivalent electric and magnetic polarization currents at an aperture in a conducting wall (a) Normal electric field at a conducting wall. (b) Electric field lines around an aperture in a conducting wall. (c) Electric field lines around electric polarization currents normal to a conducting wall. (d) Magnetic field lines near a conducting wall. (e) Magnetic field lines near an aperture in a conducting wall. (f) Magnetic field lines near magnetic polarization currents parallel to a conducting wall.

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Figure 4.31 (p. 213)Applying small-hole coupling theory and image theory to the problem of an aperture in the transverse wall of a waveguide. (a) Geometry of a circular aperture in the transverse wall of a waveguide. (b) Fields with aperture closed. (c) Fields with aperture open. (d) Fields with aperture closed and replaced with equivalent dipoles. (e) Fields radiated by equivalent dipoles for x < 0; wall removed by image theory. (f) Fields radiated by equivalent dipoles for z > 0; all removed by image theory.

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Figure 4.32 (p. 214)Equivalent circuit of the aperture in a transverse waveguide wall.

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Figure 4.33 (p. 214)Two parallel waveguides coupled through an aperture in a common broad wall.